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International Journal of Antennas and Propagation
Volume 2010 (2010), Article ID 756848, 8 pages
http://dx.doi.org/10.1155/2010/756848
Research Article

Mutual Coupling Effects on Pattern Diversity Antennas for MIMO Femtocells

School of Electronic Engineering and Computer Science, Queen Mary, University of London, London E1 4NS, UK

Received 8 December 2009; Revised 22 February 2010; Accepted 9 April 2010

Academic Editor: Hoi Shun Lui

Copyright © 2010 Yue Gao et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

Abstract

Diversity antennas play an important role in wireless communications. However, mutual coupling between multiple ports of a diversity antenna has significant effects on wireless radio links and channel capacity. In this paper, dual-port pattern diversity antennas for femtocell applications are proposed to cover GSM1800, UMTS, and WLAN frequency bands. The channel capacities of the proposed antennas and two ideal dipoles with different mutual coupling levels are investigated in an indoor environment. The relation between mutual coupling and channel capacity is observed through investigations of these antennas.

1. Introduction

Driven by demands from mobile users, there is nowadays a strong requirement to provide sustainable data rates everywhere, not just reception of signals. According to recent surveys, 50% of mobile phone calls and 70% of mobile data services will take place indoors in the next few years [1]. Using macrocells to provide coverage is expensive when serving indoor customers who require high data rates and QoS (Quality of Service). FAPs (Femtocell access points) or home-base stations [2] have been proposed in such a scenario to enhance the coverage and data rate. An FAP is a low-power access point that is built using a standard air interface (GSM, UMTS, or LTE), while the backhaul connection makes use of a broadband connection such as optical fibre or DSL (Digital Subscriber Line).

The use of femtocells benefits both users and operators. Users enjoy a better signal quality due to the proximity between transmitter and receiver. Since indoor traffic is transmitted over the IP backhaul, femtocells help the operator to manage the exponential growth of traffic and increase the reliability of macrocell networks. It has been shown from previous studies that a two-tier underlay with 50 femtocells per cell-site network can obtain a nearly 25 times improvement in overall spatial reuse compared to a macrocell-only network [2]. However, the cochannel deployment of such a large femtocell layer will impact existing macrocell networks, affecting their capacity and performance [3]. Femtocell in cochannel operation with an existing macrocellular network is technically more challenging, but is also more rewarding for the operator because of the potentially increased spectral efficiency per area through spatial frequency re-use. Especially in two-tier networks with universal frequency reuse, the near-far effect from cross-tier interference creates dead spots where reliable coverage cannot be guaranteed to users in either tier. Theoretical studies have shown that employing multiple antenna transmission at the macrocell and femtocells provides independent and spatially distinct copies of the transmitted signal, thereby providing increased spatial reuse and increased robustness against near-far effects at the user terminal [4]. In this paper, a dual-port pattern diversity antenna design is proposed for the MIMO (Multiple Input Multiple Output) femtocell application to enhance the earlier theoretical studies. Mutual coupling effects between the ports on the channel capacity are analyzed in an indoor MIMO channel model.

2. Antenna Structure and Performance

Microstrip patch antenna is generally chosen as the technology for diversity antennas for both mobile base stations and terminals because of its advantages of compactness and easy fabrication [5, 6]. This paper presents a modified circular microstrip L-probe wideband patch antenna to achieve diversity operations for FAPs based on a previous study [6]. The circular patch with a diameter of 97 mm is built on a square ground plane with a size of 160 mm by 160 mm, as shown in Figure 1(a). The patch is supported by four shorting posts, as shown in Figure 1(b). It is fed by an L-shaped probe for the conical mode and a hybrid ring (e.g., Port 4) for the broadside mode, as shown in Figure 1(c). The hybrid ring is built on an FR4 PCB (Printed Circuit Board) with a substrate thickness of 1.6 mm and permittivity of 3. Ports 2 and 3 of the hybrid ring extend two L-probes to the radiator, and Port 1 is terminated by a chip resistor. The detailed dimensions and feeding structure are shown in Figure 1(b).

fig1
Figure 1: Geometry of the proposed diversity antenna (Design 1): (a) top view, (b) side view, and (c) back view (Units in mm).

Computer Aided Design (CAD) was carried out by using the Computer Simulation Technology (CST) Microwave Studio package, which utilizes the Finite Integral Technique (FIT) for electromagnetic computation [7]. As discussed in [6], the performance of the antenna is dependent on a number of design parameters, such as antenna height, radius of the radiator, shorting posts, and hybrid ring. Based on simulations using CST Microwave studio, a prototype of this antenna has been fabricated in the Antenna Measurement Laboratory at Queen Mary University of London (QMUL).

The -parameters of the antenna were measured by an HP8720ES vector network analyzer and compared to the simulated results in Figure 2. The impedance bandwidth at  dB for both measured and simulated 11 and 22 operates from 1.7 GHz to 2.3 GHz, while at  dB it operates from 1.68 GHz to 2.5 GHz which covers GSM1800, UMTS, LTE, and WLAN. It can be seen in Figure 2 that measured 11 and 22 have the same number of resonances as those of the simulated values, and both measurement and simulation show similar amount of bandwidth at  dB. However, the main resonance of the measured 11 and 22 are shifted from that of the simulated ones by about 100 MHz. The measured 22 is also 10 dB lower than the one simulated. This variation in the impedance bandwidth is because of tolerances in the soldering and manufacturing of the connector to the hybrid ring port and the long coaxial cable used in the process of measurement.

756848.fig.002
Figure 2: Simulated and measured return losses of the antenna (Design 1).

The isolation of both measurement and simulation is around 12 dB as shown in Figure 3. The reason for this poor isolation is because the position of the frequency for matching does not always correlate to that for better isolation. It has been shown that total length of the hybrid ring has significant effects on the antenna performance [8]. For instance, when the length of the hybrid ring is exactly (where is the wavelength of the first resonance), there is always a wider bandwidth but poorer isolation. The length of the hybrid ring at is adopted in our design, which is referred to as Design 1 in the rest of paper.

756848.fig.003
Figure 3: Isolation between the conical and broadside modes.

The radiation patterns of the antenna were measured in an anechoic chamber in the Antenna Measurement Laboratory at QMUL. The measured and simulated copolarized and cross-polarized radiation patterns in the XZ-plane for broadside mode (11) at 1.7 GHz, 1.85 GHz, and 2.1 GHz are plotted in Figures 4 and 5. The measurements agree with the simulations very well. It can be seen that the copolarization is about 15 dB higher than the cross-polarization. The dominant copolarized radiation patterns in Figure 4 also have 10 dB stronger radiations in upward directions.

fig4
Figure 4: Measured () and simulated () copolarized radiation patterns for broadside mode (11) in XZ-plane at (a) 1.7 GHz, (b) 1.85 GHz, and (c) 2.1 GHz.
fig5
Figure 5: Measured () and simulated () cross-polarized radiation patterns for broadside mode (S11) in XZ-plane at (a) 1.7 GHz, (b) 1.85 GHz, and (c) 2.1 GHz.

The simulated and measured radiation patterns for the conical mode (22) at 1.7 GHz, 1.85 GHz, and 2.1 GHz are plotted in Figures 6 and 7. The measured and simulated patterns are almost identical. In comparison with the broadside mode, the radiation patterns at conical mode have a similar trend, that is the copolarization is higher than cross-polarization. However, the dominant copolarizations have nulls at the upward direction (0 degree) and stronger radiations at 50 degree elevation angles as shown in Figure 6. These patterns are complementary to those in the broadside mode in Figure 4, which indicates good pattern diversity characteristics.

fig6
Figure 6: Measured () and simulated () copolarized radiation patterns for conical mode (22) in XZ plane at (a) 1.7 GHz, (b) 1.85 GHz, and (c) 2.1 GHz.
fig7
Figure 7: Measured () and simulated () cross-polarized radiation patterns for conical mode (22) in XZ plane at (a) 1.7 GHz, (b) 1.85 GHz, and (c) 2.1 GHz.

In the case of multiantenna applications such as a diversity antenna array, it is required that the mutual coupling between multiple antennas should be minimised to maintain high efficiency of the multiple antennas [9, 10]. Further investigations were conducted using CST Microwave Studio to minimise the mutual coupling between the broadside and conical modes. As discussed earlier, the length of the hybrid ring has significant effects on the antenna performance, and there is tradeoff between the bandwidth and isolation. Design 1 with the hybrid ring length of achieved a wider bandwidth but with a 12 dB isolation; by tuning the length of the hybrid ring to , an isolation better than 30 dB over the frequency bandwidth is achieved, as shown in Figure 8. However, the impedance bandwidth is narrower than that of Design 1. The second model is referred to as Design 2. The dimensions of the hybrid ring are shown in Figure 9.

756848.fig.008
Figure 8: -parameters for the Design 2.
756848.fig.009
Figure 9: The geometry of the hybrid ring for better isolation in Design 2.

3. Mutual Coupling Effects on Channel Capacity

A ray-tracing-based channel model developed at QMUL [11] was revised to evaluate MIMO channel performance for a femtocell scenario at the 2.1 GHz band. As shown in Figure 10, the model is based on the second floor of the Electronic Engineering department at QMUL in which the building structure can be treated as a typical femtocell environment, for example, offices or home.

756848.fig.0010
Figure 10: Floor plan of the second floor of Electronic Engineering Building at QMUL.

In this model, there are three different materials that have been used to model the real environment: wood, glass, and concrete wall. All these materials are assumed to be homogenous and their material properties at 2.1 GHz are summarized in Table 1 [12].

tab1
Table 1: Material properties used at 2.1 GHz.

Different types of antennas are evaluated for the FAP in the environment of Figure 10. These antennas are (i) dual ideal dipoles separated by λ/2 (λ is the free space wavelength at 2.1 GHz), (ii) Design 1, and (iii) Design 2. Their simulated 3D radiation patterns, which are affected by the mutual coupling levels, have been imported into the model to evaluate the channel capacity. These three types of antennas and their mutual coupling level are summarized in Table 2.

tab2
Table 2: Mutual coupling levels of the antennas.

In the femtocell scenario, the bandwidth and the transmitted power for the transmitter are set to be 5 MHz and 20 dBm, respectively [13]. The FAP is placed 3.3 m high along the corridor to represent a mounted access point. Several receivers are randomly placed in different rooms, as indicated in Figure 10. Each receiver consists of two omnidirectional antennas with λ/4 spacing at the normal desk height. It is assumed that the channel is unknown to the FAP and signal to noise ratio (SNR) is 10 dB for all the cases. Mutual coupling effects for these antennas are hence evaluated in terms of channel capacity.

A MIMO system’s capacity can be calculated as [14]

where H is the normalized channel matrix, is the identity matrix and is the SNR. With a narrowband assumption, the channel response is given by [15]

where , and are the received power, phase, and time delay of the kth ray, respectively. is the total number of rays. So that for a MIMO case, channel realization the H matrix can be built as

Each of can be calculated by using (2). It has been assumed that receivers (Rx) move along the -axis as shown in Figure 10, so that all of the spatial fading possibilities are sampled across the area. The cumulative distribution function (CDF) plots for different receiver locations at Room A and Room B are shown in Figures 11 and 12, respectively.

fig11
Figure 11: CDFs for different receiver locations at Room A: (a) Rx1 and (b) Rx2.
fig12
Figure 12: CDF for different receiver locations at Room B: (a) Rx3 and (b) Rx4.

It has been observed that our proposed designs with mutual coupling effect slightly degrade channel capacity for all the cases in Room A and Room B, compared with the dual ideal dipoles which do not take into account the mutual coupling effect as shown in Figures 11 and 12. For the receivers Rx3, Design 2 with  dB mutual coupling performs slightly better than Design 1 with  dB mutual coupling. However, for the receivers Rx1, Rx2, and Rx4, Design 1 and 2 achieve almost the same capacity, which means that mutual coupling has little effects on the channel capacity when it is smaller than  dB in this case.

It is noticed in Figure 12(b) that the degradation of the channel capacity with both Design 1 and 2 is much stronger at the receiver Rx4 than any other receiving locations. The main reason for this phenomenon is because the link between the FAP and Rx4 is the longest so that propagation between the two ends experiences more scattering. Therefore, the transmitted power arrives with nearly a 360 degree pattern, as seen by the receivers, and the dipole-like radiation pattern is more suitable for such a propagation environment.

4. Conclusions

Two pattern diversity antennas operating from 1.68 GHz to 2.5 GHz for femtocell access points have been designed with mutual coupling of  dB and  dB, respectively. The channel capacity of each of these diversity antennas is evaluated in an indoor MIMO channel environment and compared with that of dual ideal dipoles with no mutual coupling effect. It has been shown that the channel capacity of the proposed Design 2 with very low mutual coupling ( dB) is close to that of an ideal dipole array without mutual coupling in most cases. The exception case from the results shows that the channel capacity not only depends on the mutual coupling levels but also on the propagation environment. The channel capacity of the proposed Design 1 with a mutual coupling of  dB achieved the similar capacity as that of Design 2. Therefore, it can be concluded that a mutual coupling of  dB is a reasonable level to maintain a good channel performance, and there is no need to obtain a very low mutual coupling in Design 2 at the expense of the diversity antenna performance, such as impendence bandwidth and compactness.

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