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International Journal of Navigation and Observation

Volume 2008 (2008), Article ID 372651, 11 pages

http://dx.doi.org/10.1155/2008/372651

## Bayesian Time Delay Estimation of GNSS Signals in Dynamic Multipath Environments

^{1}Vodafone Chair Communications Systems, Dresden University of Technology, TU Dresden, 01062 Dresden, Germany^{2}German Aerospace Center DLR, Institute of Communications and Navigation, Oberpfaffenhofen, 82234 Wessling, Germany

Received 1 August 2007; Revised 7 December 2007; Accepted 17 March 2008

Academic Editor: Letizia Presti

Copyright © 2008 Michael Lentmaier et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

#### Abstract

A sequential Bayesian estimation algorithm for multipath mitigation is presented, with an underlying movement model that is especially designed for dynamic channel scenarios. In order to facilitate efficient integration into receiver tracking loops, it builds upon complexity reduction concepts that previously have been applied within maximum likelihood (ML) estimators. To demonstrate its capabilities under different GNSS signal conditions, simulation results are presented for both BPSK-modulated and BOC-(1,1) modulated navigation signals.

#### 1. Introduction

A major error source within global navigation satellite systems (GNSSs) comes from multipath, the reception of additional signal replica due to reflections, which introduce a bias into the estimate of the delay lock loop (DLL) of a conventional navigation receiver. For efficient removal of this bias, it is possible to formulate advanced maximum likelihood (ML) estimators that incorporate the echoes into the signal model and are capable of achieving the theoretical limits given by the Cramér Rao bound. The drawback of ML estimator techniques is that the parameters are assumed to be constant during the time of observation. Independent estimates are obtained for successive observation intervals, whose length has to be adapted to the dynamics of the channel.

In this paper, we consider the important practical case of dynamic channel scenarios and assess how the time-delay estimation can be improved if information is available about the temporal evolution of the channel parameters. Our approach is based on Bayesian filtering, the optimal and well-known framework to address such dynamic state estimation problems [1]. Sequential Monte Carlo (SMC) methods [2, 3] are used for computing the posterior probability density functions (PDFs) of the signal parameters.

#### 2. A Comparison of Various Multipath Mitigation Approaches

Figure 1 gives an overview of the relationships
between different multipath mitigation and estimation approaches. In fact, we
have chosen to discriminate approaches according to their primary objective.
The left column represents the class of techniques that attempt to *mitigate* the effect of multipath in different ways. This can for example be achieved by
modifications of the antenna response, either by means of hardware design or
with signal processing techniques (e.g., beamforming). The majority of the
remaining mitigation techniques are in some way aligning the more or less
traditional receiver components (e.g., the early/late correlator) to the signal
received in the multipath environment. The probably most simple technique is
the adjustment of the correlator spacing applied in the Narrow Correlator
[4]. Other well-known
examples of this category are the Strobe Correlator [5], the Gated Correlator
[6], or the Pulse
Aperture Correlator [7]. To incorporate new signal forms (such as BOC), these
methods need “tuning” in order to suffer as little as possible from
multipath. On the other hand, multipath *estimation* techniques (right column) treat multipath (in particular the delay of the
paths) as something to be estimated from the channel observations, so that its
effects can be trivially removed at a later processing stage. For the
estimation techniques, we have differentiated between *static* and *dynamic* approaches, according to the underlying assumption of the channel dynamics.
Examples for static multipath estimation are those belonging to the family of
ML estimators, often using different efficient maximization strategies over the
likelihood function [8–13].
For static channels without availability of prior information, the ML approach
is optimal and performs significantly better than other techniques, especially
if the echoes have short delay. An estimator based on sequential importance
sampling (SIS) methods (particle filtering) for static multipath scenarios has
been considered in [14], which has the advantage that prior channel knowledge
can be incorporated.

As a first step towards addressing dynamic channels, one can incorporate ML estimators in receiver loops or formulate quasisequential estimators [15, 16]. Finally, dynamic estimators that target the computation of the posterior PDF conditioned on the received channel output sequence at the receiver can be applied on a per single range basis or operate in the position domain. In this paper, we concentrate on dynamic estimators applied per each range. The sequential Monte Carlo approach has also been suggested in the communications field for estimation of time-varying channel responses in spread spectrum systems [17, 18].

#### 3. Signal Model

Assume that the complex valued baseband-equivalent received signal is equal to where is a
delta-train code sequence that is modulated on a pulse , is the maximum
number of allowed paths reaching the receiver (to restrict the modeling
complexity), is a binary
function that controls the activity of the th path, and and are their
individual complex amplitudes and time delays, respectively. The signal is
disturbed by additive white Gaussian noise . Grouping blocks of samples at
times , , together into vectors , whilst assuming
the parameter functions , and being constant
within the corresponding time interval and equal to , , and , this can be rewritten asIn the compact form on the right
hand side, the samples of the delayed pulses are stacked
together as columns of the matrix , is a matrix
representing the convolution with the code, and the delays and amplitudes are
collected in the vectors and , respectively.
Furthermore, for concise notation we use whilst the
elements of the vector , , determine whether the th path is
active or not by being either corresponding
to an active path or for a path that
is currently not active. The term denotes the
signal hypothesis and is completely determined by the channel parameters , and . Using
(2), we can write the associated *likelihood
function* asThe likelihood function will
play a central role in the algorithms discussed in this paper; its purpose is
to quantify the conditional probability of the received signal conditioned on
the unknown signal (specifically the channel parameters).

#### 3.1. Efficient Likelihood Computation

In [11], a general concept for the efficient representation
of the likelihood (3) was presented, which is applicable to many of the
existing ML multipath mitigation methods. The key idea of this concept is to
formulate (3) through a vector resulting from
an orthonormal projection of the observed signal onto a smaller
vector space, so that is a sufficient
statistic according to the Neyman-Fisher factorization [19] and hence suitable for
estimating . In other words, the reduced signal comprises the
same information as the original signal itself. In practice, this concept
becomes relevant as the projection can be achieved by processing the received
signal (2) with a bank of correlators and a subsequent decorrelation of the
correlator outputs. A variant of this very general concept, applied in
[13], has also been
referred to as the *Signal Compression Theorem* in [20] for a set of special projections that do not require
the step of decorrelation due to the structure of the used correlators. For
instance, unlike the correlation technique used in [8], the one suggested in [13] already projects onto an
orthogonal and thus uncorrelated subspace, similar to the code matched
correlator technique proposed in [11]. Due to complexity reasons, all practically relevant
realizations of ML estimators [8, 13] operate in a projected space, namely after
correlation. The corresponding mathematical background will be discussed below,
including also interpolation of the likelihood and elimination of complex
amplitudes as further methods for complexity reduction.

#### 3.1.1. Data Compression

As explained above, the large vector containing the
received signal samples is linearly
transformed into a vector of much smaller
size. Following this approach, the likelihood according to (2) can be rewritten
aswith the compressed received
vector and the
compressed signal hypothesis :and the orthonormal compression
matrix , which needs to fulfillto minimize the compression
loss. According to [11], the compression can be two-fold so that we can
factorizeinto a *canonical component
decomposition*, given by an matrix , and a *principal component decomposition*,
given by an matrix . In [11], two choices for are
proposedwhere the elements of the vector define the
positions of the individual correlators. The noise-free outputs of the
corresponding correlator banks are illustrated in Figure 2. To decorrelate the bank
outputs and , as mentioned above, the whitening matrix can be obtained
from a QR decomposition of and respectively.
Apart from practical implementation issues, both correlation methods given by
(8) are equivalent from a conceptual point of view. For details on the
compression through the reader is
referred to [11].

#### 3.1.2. Interpolation

In order to compute (4) independently of the sampling grid, advantage can be made of interpolation techniques. Using the discrete Fourier transformation (DFT), with being the DFT matrix and being its inverse counterpart (IDFT), we getwith being a matrix of column-wise stacked vectors with Vandermonde structure [10, 11], such that the element at row and column computes with is the length of the pulse in samples. The advantage of the interpolation is that it can take place in the reduced space. The most costly computations in (9) can be carried out in precalculations as the matrix , whose row dimension corresponds to the dimension of the reduced space and whose column dimension is , is constant.

#### 3.1.3. Amplitude Elimination

In a further step, we reduce the number of parameters by optimizing (4) for a given set of and with respect to the complex amplitudes , which can be achieved through a closed-form solution. Usingand obtaining by removing zero columns from one yields the corresponding amplitude values of the active paths:As we have introduced a potential source of performance loss by eliminating the amplitudes and thus practically are disregarding their temporal correlation, we propose to optimize (4) usingwith the adjustable averaging coefficient . When evaluating (4), we substitute bywhere the elements of the vector that are indicated to have an active path () are set equal to the corresponding elements of . All other elements () can be set arbitrarily as their influence is masked by the zero elements of .

#### 3.2. Review of the ML Concept

The concept of ML multipath estimation has drawn substantial research interest since the first approach was proposed in [8]. Despite being treated differently in various publications, the objective is the same for all ML approaches, namely to find the signal parameters that maximize (3) for a given observation :The signal parameters are thereby assumed as being constant throughout the observation period . Different maximization strategies exist, which basically characterize the different approaches. Despite offering great advantages for theoretical analysis, the practical advantage of the generic ML concept is questionable due to a number of serious drawbacks.(i) The ML estimator assumes that the channel is static for the observation period and is not able to exploit its temporal correlation throughout the sequence . Measured channel scenarios have shown significant temporal correlation [21].(ii) Despite being of great interest in practice, the estimation of the number of received paths is often not addressed. The crucial problem here is to correctly estimate the current number of paths to avoid over determination, since an overdetermined estimator will tend to use the additional degrees of freedom to match the noise by introducing erroneous paths. There exist various techniques based on model selection that can be employed to estimate the number of paths [22] but they suffer from the problem of having to dynamically adjust the decision thresholds. Typically, only a single hypothesis is tracked, which in practice causes error event propagation.(iii) The ML estimator does only provide the most likely parameter set for the given observation. No reliability information about the estimates is provided. Consequently, ambiguities and multiple modes of the likelihood are not preserved by the estimator.

ML estimators require that the estimated parameters remain constant during the observation period. Due to data modulation and phase variations in practice, this period, which is often referred to as the coherent integration time, is limited to a range of 1 millisecond–20 milliseconds. To reach a sufficient noise performance with a ML estimator in practice, it is required to extend its observation interval approximately to the equivalent averaging time of a conventional tracking loop, which is commonly in the order of several hundred coherent integration periods. To overcome this problem, the observations are forced to be quasicoherent by aiding the ML estimator with a phase locked loop (PLL) and a data removal mechanism [8].

#### 4. Sequential Estimation

#### 4.1. Optimal Solution

In Section 3,
we have established the models of the underlying time variant processes. The
problem of multipath mitigation now becomes one of *sequential estimation of
a hidden Markov process*. We want to estimate the unknown channel parameters
based on an evolving sequence of received noisy channel outputs . The channel process for each range of a satellite
navigation system can be modeled as a first-order Markov process if future
channel parameters given the present state of the channel and all its past
states depend only on the present channel state (and not on any past states).
We also assume that the noise affecting successive channel outputs is
independent of the past noise values; so *each channel observation depends
only on the present channel state*.

Intuitively, we are exploiting not only the channel observations to estimate the hidden channel parameters (via the likelihood function), but we are also exploiting our prior knowledge about the statistical dependencies between successive sets of channel parameters. We know from channel measurements that channel parameters are time varying but not independent from one time instance to the next; for example, an echo usually experiences a “life-cycle” from its first occurrence, then a more or less gradual change in its delay and phase over time, until it disappears [21]. These measurements also show that the common channel models considered in communication systems [17, 18] are not adequately reflecting the properties that are crucial for high-resolution signal delay estimation as required in navigation systems.

Now that our major assumptions have been established,
we may apply the concept of *sequential Bayesian estimation*. The reader
is referred to [23]
which gives a derivation of the general framework for optimal estimation of
temporally evolving (Markovian) parameters by means of inference, and we have
chosen similar notation. The entire history of observations (over the temporal
index ) can be
written asSimilarly, we denote the
sequence of parameters of our hidden Markovian process byHere, represents the
characterization of the hidden channel state, including the parameters that
specify the signal hypothesis given in
(2).
Our goal is to determine the posterior PDF of every possible channel
characterization given all channel observations: (see Figure 3).
Once we have evaluated this posterior PDF, we can either determine that channel
configuration that maximizes it—the so-called maximum a posteriori (MAP) estimate;
or we can choose the expectation—equivalent to the minimum mean square error
(MMSE) estimate. In addition, the posterior distribution itself contains all
uncertainty about the current range and is thus the optimal measure to perform
sensor data fusion in an overall positioning system.

It can be shown that the sequential estimation
algorithm is recursive, as it uses the posterior PDF computed for time instance to compute the posterior
PDF for instance (see Figure 4).
For a given posterior PDF at time instance , , the prior PDF is calculated
in the so-called *prediction step* by applying the Chapman-Kolmogorov
equation:with being the state
transition PDF of the Markov process. In the *update step,* the new
posterior PDF for step is obtained by
applying Bayes' rule to yielding the
normalized product of the likelihood and the prior
PDF:The term follows from
(4) and represents the probability of the measured channel output (often
referred to as the likelihood value), conditioned on a certain configuration of
channel parameters at the same time step . The denominator of (19) does not depend on and so it can
be computed by integrating the numerator of (19) over the entire range of (normalization).

To summarize so far, the entire process of prediction and update can be carried out recursively to calculate the posterior PDF (19) sequentially, based on an initial value of . The evaluation of the likelihood function is the essence of the update step. Similarly, maximizing this likelihood function (i.e., ML estimation) would be equivalent to maximizing only in the case that the prior PDF does not depend on and when all values of are a priori equally likely. Since these conditions are not met, evaluation of entails all the above steps.

#### 4.2. Sequential Estimation Using Particle Filters

The optimal estimation algorithm relies on evaluating
the integral (18), which is usually a very difficult task, except for certain
additional restrictions imposed on the model and the noise process. So, very
often a suboptimal realization of a Bayesian estimator has to be chosen for
implementation. In this paper, we use a sequential Monte Carlo (SMC) filter, in
particular a sampling importance resampling particle filter (SIR-PF) according
to [23]. In this
algorithm, the posterior density at step is represented
as a sum and is specified by a set of particles:where each particle with index has a state and has a *weight*. The sum over all particles' weights is one. In
SIR-PF, the weights are computed according to the principle of *importance
sampling* where the so-called proposal density is chosen to be , and with *resampling* at every time step. For the approximate
posterior approaches the true PDF.

The key step, in which the *measurement* for
instance is
incorporated, is in the calculation of the weight which for the
SIR-PF can be shown to be the likelihood function: . The characterization of the *channel process* enters in the algorithm, when at each time instance , the state of each particle is drawn
randomly from the proposal distribution, that is, from .

#### 4.3. Exploiting Linear Substructures

If there exist linear substructures in the model, it is possible to reduce the computational complexity of the filter by means of marginalization over the linear state variables [24], also known as Rao-Blackwellization [25]. In a marginalized filter, particles are still used to estimate the nonlinear states, while for each of the particles the linear states can be estimated analytically. In our case, since the measurement is a linear function of the complex amplitudes , the likelihood function can be factorized aswhere the function is Gaussian with respect to , and is proportional to . Marginalization of (21) over the linear state variables givesAssuming that the amplitudes are block-wise independent (), it follows that the weights of the SIR particle filter are equal to , which is given by (4).

If there exists a temporal correlation of the amplitudes, an optimal marginalized filter requires the implementation of a separate Kalman filter for each of the particles. As we do not want to increase the complexity per particle, we take the correlation into account by adjustment of in (13).

#### 4.4. Choice of Appropriate Channel Process

To exploit the advantages of sequential estimation for
our task of multipath mitigation/estimation, we must be able to describe the
actual channel characteristics (channel parameters) so that these are captured
by . In other words, the model must be a first-order
Markov model, and all transition probabilities must be known. In our approach,
we approximate the channel as follows.(i) The channel is
totally characterized by a direct path (index ) and at most echoes,(ii)each path has
complex amplitude and relative
delay and ; where echoes are constrained to have delay , that is, ,(iii)the different
path delays follow the process:(iv) each parameter that specifies
the speed of the change of the path delay follows its own
process:(v)the magnitudes
and phases of the individual paths, represented by the complex amplitudes , are eliminated according to (12) and (14) for the
computation of the likelihood (4),(vi) each path is
either “on” or “off,” as defined by channel parameter “on,” “off” ,(vii) where follows a
simple two-state Markov process with a-symmetric crossover and same-state
probabilities: The model
implicitly incorporates three i.i.d noise sources: Gaussian and as well as the
noise process driving the state changes for . These sources provide the randomness of the model.
The parameter defines how
quickly the speed of path delays can change (for a given variance of ). Finally, is the time
between instances and . We assume all *model parameters* (i.e., , , noise variances, and the “on”/“off”
Markov model) to be independent of (see Figure 5).
The hidden channel state vector can therefore
be represented asNote that the model implicitly
represents the number of pathsas a time-variant parameter.

When applied to our particle filtering algorithm, drawing from the proposal density is simple. Each particle stores the above-channel parameters of the model, and then the new state of each particle is drawn randomly from which corresponds to drawing values for and as well as propagating the “on”/“off” Markov model, and then updating the channel parameters for according to (23)–(26).

#### 4.5. Practical Issues

#### 4.5.1. Model Matching

It is important
to point out that a sequential estimator is only as good as its state
transition model matches the real world situation. The state model needs to
capture *all* relevant hidden states with memory and needs to correctly
model their dependencies, while adhering to the first order Markov condition.
Furthermore, any memory of the measurement noise affecting the likelihood
function must be
explicitly contained as additional states of the model , so that the measurement noise is i.i.d.

The channel state model is motivated by channel modeling work for multipath prone environments such as the urban satellite navigation channel [21, 26]. In fact, the process of constructing a channel model in order to characterize the channel for signal level simulations and receiver evaluation comes close to our task of building a first-order Markov process for sequential estimation. For particle filtering, the model needs to satisfy the condition that one can draw states with relatively low computational complexity. Adapting the model structure and the model parameters to the real channel environment is a task for current and future work. It may even be possible to envisage hierarchical models in which the selection of the current model itself follows a process. In this case, a sequential estimator will automatically choose the correct weighting of these models according to their ability to fit the received signal.

#### 4.5.2. Integration into a Receiver

For receiver integration, the computational complexity of the filtering algorithm is crucial. From a theoretical point of view, it is desirable to run the sequential filter clocked corresponding to the coherent integration period of the receiver and with a very large number of particles. From the practical point of view, however, it is desirable to reduce the sequential filter rate to the navigation rate and to minimize the number of particles. Existing ML approaches can help here to achieve a flexible complexity/performance tradeoff, as strategies already developed to extend the observation periods of ML estimators can be used directly to reduce the rate of the sequential filtering algorithm.

#### 5. Performance Evaluation

To demonstrate the capabilities of the SMC-based Bayesian time delay estimator proposed in Section 4, we have carried out computer simulations for both static and dynamic channel environments. The signal-to-multipath ratio (SMR) was chosen constant and equal to dB, while the relative phases are changing according to with MHz being the frequency of the L1 carrier. The Bayesian estimator uses a time interval of millisecond corresponding to the duration of a codeword. The amplitude averaging coefficient is set to and signal compression is applied with (code-matched correlators) . The channel parameters , , , and are selected to fit the statistics of a real channel according to [21]. The SIR-PF uses the minimum mean square error (MMSE) criterion to estimate the parameters from the posterior.

#### 5.1. Static Multipath Scenario

The capability of multipath mitigation techniques is commonly assessed by showing the systematic error due to a single multipath replica plotted as a function of the relative multipath delay in a static channel scenario. In Figure 6, the root mean square error (RMSE) is shown for the proposed sequential estimator, implemented as a SIR-PF with particles. For comparison, the performance of conventional DLLs with Narrow Correlator and with Strobe Correlator is also shown. The simulated signal corresponds to a GPS L1 signal with being a Gold code of length 1023 that is modulated on a bandlimited rectangular pulse. The chip rate is 1.023 Mchips/s so that the duration of the codeword is 1millisecond. The one-sided bandwidth of the resulting navigation signal is 5 MHz. Estimators with fixed two-path model or fixed single path model are also shown for comparison with the implicit path activity tracking. The performance of a single path estimator is comparable to that of a DLL with infinitesimal correlator spacing and shows a considerable bias over a large delay range. The estimator with fixed two-path model successfully mitigates the multipath bias for delays greater than 30 m. However, for smaller delays it shows an increasing variance and is outperformed by the single path estimator. The estimator with path activity tracking is capable of combining the advantages of both models. From the posterior, it is possible to calculate the estimated average probability of a two-path model, which is shown in Figure 7, and indicates the transition between the models: for small delays the two paths essentially merge to a single one. Note that in these simulations, the model parameters of the sequential estimator are still the ones designed for the dynamic channel and not optimal for this static scenario. The RMSE as function of the number of particles is shown in Figure 8 for a relative multipath delay of 14 m, which corresponds to the worst case in Figure 6.

#### 5.2. Dynamic Scenario

The dynamic multipath channel scenario with up to paths, used in the following simulations and depicted in Figure 9, has been generated according to the movement model, whereby the parameters , , , and were chosen to resemble a typical urban satellite navigation channel environment [26].

Figure 10 shows for this multipath scenario at a carrier-to-noise ratio of dB-Hz the BPSK and the BOC-(1,1) performance of a DLL with a narrow correlator spacing of seconds, corresponding to a tenth of a code chip. A DLL loop bandwidth of 1 Hz was selected, which appeared to deliver the best DLL performance for this channel. For a fair comparison of the different modulation techniques, both signals were generated with the same C/A code sequence of length 1023, the same receiver bandwidth of 5 MHz (one-sided), a sampling rate of MHz, and a coherent integration time of millisecond. Although the results show an improvement for the BOC-(1,1) modulation, there still remains a considerable error due to the multipath. This behavior is confirmed by a comparison with the multipath error envelope, depicted in Figure 11. While in some multipath delay regions, the error is reduced by the BOC-(1,1) modulation (see, e.g, the segment marked by the dashed box in Figure 10), more sophisticated multipath mitigating techniques are required to reduce the errors due to short range multipath.

The simulation results for the particle filter-based estimator with particles are given in Figures 12(a) and 12(b) for the same channel as in Figure 10. They show that the performance could be improved substantially, resulting in a reduction of the root mean square (RMS) error from 3.77 m to 0.769 m for BPSK modulation and from 2.61 m to 0.694 m for BOC(1,1) modulation, respectively.

The RMSE as function of the number of particles is shown in Figure 13.

#### 6. Conclusions

We have demonstrated how sequential Bayesian estimation techniques can be applied to the multipath mitigation problem in a navigation receiver. The proposed approach is characterized by code-matched, correlator-based signal compression together with interpolation techniques for efficient likelihood computation in combination with a particle filter realization of the prediction and update recursion. The considered movement model has been adapted to dynamic multipath scenarios and incorporates the number of echoes as a time variant hidden channel state variable that is tracked together with the other parameters in a probabilistic fashion. A further advantage compared to ML estimation is that the posterior PDF at the output of the estimator represents reliability information about the desired parameters and preserves the ambiguities and multiple modes that may occur within the likelihood function. Simulation results for BPSK- and BOC-(1,1) modulated signals show that in both cases significant improvements can be achieved compared to a DLL with narrow correlator. In this work, we have employed two methods to reduce complexity: the signal compression to facilitate the computation of the likelihood function as well as a simple form of Rao-Blackwellization to eliminate the complex amplitudes from the state space. Further work will concentrate on additional complexity reduction techniques such as more suitable proposal functions or particle filtering algorithms such as the auxiliary particle filter that are possibly more efficient with respect to the number of particles when applied to our problem domain.

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