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Mathematical Problems in Engineering
Volume聽2012聽(2012), Article ID聽520296, 13 pages
http://dx.doi.org/10.1155/2012/520296
Research Article

Bifurcations in a Generalization of the ZAD Technique: Application to a DC-DC Buck Power Converter

1Percepci贸n y Control Inteligente, Departamento de Ingenier铆a El茅ctrica, Facultad de Ingenier铆a y Arquitectura, Universidad Nacional de Colombia, Sede Manizales, Electr贸nica y Computaci贸n, Bloque Q, Campus La Nubia, Manizales, Colombia
2ABC Dynamics, Departamento de Matem谩ticas y Estad铆stica, Facultad de Ciencias Exactas y Naturales, Universidad Nacional de Colombia, Sede Manizales, Bloque Y, Campus La Nubia, Manizales, Colombia

Received 21 March 2012; Accepted 30 April 2012

Academic Editor: Ahmad M.聽Harb

Copyright 漏 2012 Ludwing Torres et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

Abstract

A variation of ZAD technique is proposed, which is to extend the range of zero averaging of the switching surface (in the classic ZAD it is taken in a sampling period), to a number of sampling periods. This has led to a technique that has been named -ZAD. Assuming a specific value for , we have studied the 2-ZAD technique. The latter has presented better results in terms of stability, regarding the original ZAD technique. These results can be demonstrated in different state space graphs and bifurcation diagrams, which have been calculated based on the analysis done about the behavior of this new strategy.

1. Introduction

Currently, power electronics has an important place in industry. This is largely due to the very extensive number of applications derived from these systems, including control of power converters. This was the main motivation for researchers worldwide to develop new advances in this field and has promoted the investigation on many mathematical models. They correspond usually to variable structure systems, chaos, and control. The practical goal is to obtain better devices or new and improved mechanisms for use in electronic controllers.

Bifurcation, chaos, and control in electronic circuits have been reported in many papers such as [1, 2]. Regarding power electronics, early works can be found in the literature from the 1980s when first observed in [3, 4]. In 1989 several authors such as Krein and Bass [5], and Deane and Hamill [6] began to study chaos in various power electronic circuits. In his work Wood [7] contributed to the understanding of chaos, showing in phase diagrams that the pattern of the trajectories was messy as small variation on initial conditions and parameters in the system were performed. Meanwhile Deane and Hamill reported some of the best works on bifurcations and chaos applied to electronic circuits. Their studies were based on computer simulations and laboratory experiments [3, 4, 6].

Because of the multiple side effects that generation of chaos caused in these systems, several authors proceeded to develop different control techniques, such as [8] by Ott et al., who found a way of controlling unstable orbits coexisting with chaos. They used small disturbances. This resulted in the so well-known OGY method (after the names of the authors Ott, Grebogi, and Yorke). Pyragas [9] contributed to this topic with a feedback scheme using a time-delayed control known as (time-delayed autosynchronization) TDAS.

Also the work by Utkin is very important in the control literature. He studied (pulse-width modulation) PWM systems and variable structure systems [10]. He introduced a now very popular control technique so-called sliding-mode control (SMC) and many applications were proposed [11]. These studies were taken later as a starting point by Carpita et al. [12]. In his work, Carpita presents a sliding mode controller for a (uninterrupted power system) UPS. Carpita uses a sliding surface which is a linear combination of error variable and its derivative.

Some time after, a new technique, both conceptually different from sliding-mode control (although very related to it) and as a practical implementation to SMC, appeared. It was called (zero average dynamics) ZAD by the authors. This control technique forces the system to have, at each clock cycle, a zero average of the sliding surface (instead to be zero all the time, as in sliding-mode control). Application of this technique to a buck converter with centered pulse and an approximation scheme needed for the practical implementations [12] has obtained very good performance. Robustness, low stationary error, and fixed switching frequency have also been achieved [13]. It has been observed that as the main parameter in the surface is decreased, chaotic behavior appears which is not desirable in practice. Then, several additional techniques such as TDAS (mentioned before) or (fixed point induced control) FPIC must be implemented in order to guarantee a wider operation range [13]. FPIC has obtained the best results with regards to stabilization and chaos control. Bifurcation diagrams have shown flip or period-doubling bifurcations followed by border-collision bifurcations due to the saturation of the limit cycle. This sequence of bifurcations leads the system to chaotic operation for low values of . When saturation of the limit cycle appears, the ZAD technique is degraded and thus zero average in each cycle is lost.

In order to solve this problem, we generalize the ZAD technique (from now on called classical ZAD) to the so-called -ZAD technique. This generalization allows the surface to be of zero average not in every cycle (as classical ZAD), but in a sequence of cycles. Being a weaker condition one can choose the duty cycles in such a way that they are not saturated (at least not so frequently) and thus zero average and stabilization in a periodic orbit is obtained.

Specifically, our study has focused on the value , which gives rise to 2-ZAD, that is, two sampling periods for the zero average in the surface. We compare this generalization with the classical ZAD through bifurcation diagrams.

The remaining of this paper is organized as follows. In Section 2 we explain in detail mathematical modelling of this technique and we perform the corresponding algebraic computations. In Section 3 the numerical implementation and the results are discussed. Finally, conclusions and future work are stated in Section 4.

2. -ZAD Strategy

The scheme for the buck converter is shown in Figure 1. We donot take into account the diode full dynamics and thus we assume always continuous conduction mode (alternatively, we can consider bidirectional switches which allow negative currents).

520296.fig.001
Figure 1: Scheme of the Buck converter.

The classical diode-transistor scheme is changed by a transistors bridge linked with the source. When transistors are in (1) position the pulse magnitude is , and when the position is (2.2), then the magnitude is . As a result we have a PWM system which inverts the polarity at each switching.

With the aim of obtaining a nondimensional system with nondimensional parameters, which leads to easier analysis, we perform the following change of variables [13]:

Also we normalize the sampling period where , , , , and . These values come from laboratory prototypes which can be found in the literature [13]. Thus we get the value and the following nondimensional system: which can be written in compact form as where

The solution of this piecewise-linear system can be computed algebraically and the expression for the Poincar茅 map corresponding to sampling every time units is [14] stands for the control action, which corresponds to a centered pulse, which can be mathematically written as corresponds to the so-called duty cycle. It will be computed in such a way that the dynamical system tends to the sliding surface defined as

The ZAD technique imposes that the orbit must be such that when the variables are replaced in the sliding surface in (2.7), the following equation is fulfilled:

Computing from (2.8) involves transcendental expressions which should be avoided in practical applications. Thus in the literature, the sliding surface has been approximated by a piecewise-linear function. This allows an algebraic solution for , which is used in applications.

2.1. Computations for the Classical ZAD Strategy

Figure 2 shows how the classical ZAD strategy works. The area under the curve must be zero.

520296.fig.002
Figure 2: Scheme for the classical ZAD strategy.

Using the piecewise-linear approximation, the integral can be written as where is the value of the sliding surface at the sampling instant, is the derivative in the first and third pieces of the piecewise-linear approximation and is the derivative in the central piece. After some algebra we get

Since a value or is practically impossible, when this occurs the duty cycle is saturated in such a way that we take if and we take if . In those cases where is saturated the ZAD strategy fails and thus the zero average condition is not fulfilled.

2.2. Computations for the -ZAD Strategy

Now we consider the computations when the zero average condition is weakened to a sequence of cycles instead of every cycle. Previously, with the classical ZAD strategy we had Now, with the -ZAD strategy, we have

This means that we extend the condition of zero average to an interval of consecutive cycles.

2.3. Computations for the 2-ZAD Strategy

In the case we get In Figure 3 we depict a scheme for the 2-ZAD. The area under the curve between and must be zero.

520296.fig.003
Figure 3: Scheme for the 2-ZAD technique.

Since we are now dealing with two cycles, we can have two different duty cycles and different values for the derivatives of the piecewise-linear functions. Thus we introduce the following notation.

(i)In the first cycle we write for the duty cycle and we write for the duty cycle in the second cycle. (ii)For the derivatives we use and for the first cycle. They correspond to and for the first cycle. They are computed according to the sign of and are sampled at the beginning of the first interval (i.e., at ). In the second interval we will denote the derivatives by and . They correspond to and for the second interval. They are computed sampling at the beginning of the second cycle (i.e., at ) as it is shown in Figure 3.

With this notation and some further algebra, we get For the second piece of the first cycle , with derivative we get For the third piece of the first interval, with derivative , we get For the second cycle we have derivatives and and the duty cycle . In the first piece of the second cycle , with derivative , we get For the second piece in the second cycle , with derivative , we get Finally, for the third piece in the second interval , with derivative , we get Thus we have

Solving the integral we have the following expression for as a function of :

Since we have as an independent variable and is dependant of , we can assume that is nonsaturated. Then our proposal is to choose to be as the optimal value (in a certain sense) taking between and . Our optimal condition will be choosing the closest to the stationary theoretical value as possible. In this way we approximate to the desired regulation value as much as possible.

3. Numerical Results

Following [13] the stationary theoretical value for the duty cycle was computed as

Then according to the previous section, the following results are obtained.

3.1. Results

In the literature it was found that, for the classical ZAD strategy and centered pulse, stability of the -periodic orbit was obtained in the range , approximately. Below this value, period doubling and border collision bifurcation due to saturations lead the system to big amplitude chaotic operation, which is inadmissible in practical devices. The ranges considered for the 2-ZAD strategy contain values from to . We can observe the transition from stability to chaos.

Figure 4 shows bifurcations obtained for the classical ZAD strategy, for parameter values less than . For parameter values greater than 3.23, the -periodic orbit is stable. The duty cycle is approximately when and . In the figures we observe that chaos is obtained when decreases. For parameter values less than , big amplitude chaos appears. The regulation error also grows. Close to we can also observe a fast transition of the stable -periodic orbit into saturation.

fig4
Figure 4: Bifurcation diagram with bifurcation parameter , in the classical ZAD strategy.

In the computations corresponding to Figure 5 we considered 2-ZAD strategy all the time, for all values of parameter . We allowed saturations when it was impossible to get two nonsaturated duty cycles. In these figures it can be observed that the stability range of the -periodic orbit is wider than that for the classical ZAD strategy. From until approximately the 2-ZAD strategy avoids the orbit to get far from the stable -periodic orbit. This is mainly due to the existence of nonsaturated duty cycles.

fig5
Figure 5: Bifurcation diagrams with bifurcation parameter when 2-ZAD strategy is considered.

Figures 6, 7, 8, and 9 correspond to a reference value and initial conditions and (stable state values according to [13]). Initial conditions close to the stable state value are considered in order to check the performance of these techniques. With the aim of getting a better insight of the behavior of the orbit in stable state, we take the last values of the trajectory. Thus we compare both the classical ZAD strategy with 2-ZAD. Results show that 2-ZAD performs much better than classical ZAD technique.

fig6
Figure 6: 2-ZAD strategy for and initial conditions close to the reference value.
fig7
Figure 7: Classical ZAD strategy for and initial conditions close to the reference value.
fig8
Figure 8: 2-ZAD strategy for and initial conditions close to the reference value.
fig9
Figure 9: Classical ZAD strategy for and initial conditions close to the reference value.

Regarding chaotic behavior, Figure 10 shows the Lyapunov exponents for both techniques. It can be observed that in the 2-ZAD case the exponents are below zero for a wider range than for the classical ZAD strategy. For the 2-ZAD, stability is kept almost until close to . Then some small amplitude period-doubling bifurcations appear. Close to and below, saturation in the duty cycle cannot be avoided and chaos appears.

fig10
Figure 10: Comparison of Lyapunov exponents.

4. Conclusions and Future Work

A generalization of the so-called ZAD technique (named -ZAD) was described. It can be used as an alternative to classical ZAD when saturation effects lead the system to big amplitude chaotic behavior. In fact, 2-ZAD shows better performance than classical ZAD in all cases (regarding stability and nonsaturation). Even it can be used without additional stabilization methods such as FPIC or TDAS. Thus the control algorithm becomes simpler. Good performance of -ZAD is mainly dependent on the way that the (independent) duty cycles are computed. Several criteria can be chosen. The one chosen in this paper showed very good success. But it is worth to note that different criteria will lead to probably very different dynamics. Thus even better results than those shown in this paper can be obtained.

It is expected that as the value of is increased, better results can be obtained. But also it is evident that the control algorithm gets more complex. Some early results with 3-ZAD (not shown in this paper) confirm this last sentence. Anyway, trying values bigger than 2 with some sort of optimal condition is proposed as our next step into further understanding the ZAD strategy.

Acknowledgments

The authors acknowledge partial financial support to CeiBA Complexity and to the prject Dima-vicerrector铆a de investigaci贸n no. 20201006570 鈥淐谩lculo Cient铆fico para Procesamiento Avanzado de Biose帽ales鈥.

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