On the Development of High Power DC-DC Step-Down Converter with Energy Recovery Snubber

Abstract

The effect of switching losses on the efficiency of a switch mode power converter and methods adopted for its improvement using an energy recovery lossless snubber has been presented. A comparative analysis of various types of soft switching techniques along with effects of dissipative and nondissipative snubbers on efficiency of the converter has been carried out before zeroing in on the selected scheme. The selected snubber serves the dual function of a turn-on and turn-off snubber and thereby reducing the switching losses both during turn-on and turn-off transients, resulting in improved efficiency of the converter. A detailed design procedure of the snubber for high-power applications taking into account various effects such as diode reverse recovery, diode voltage stress, and minimum and maximum duty cycle limits, has been presented in this paper. Importance of practical aspects in layout to minimize wiring inductance is also highlighted. A high-power prototype of buck converter has been developed to experimentally validate the theoretical design and analytical observations.

1. Introduction

Switch mode power supplies are popular because of higher efficiency, smaller size, and lighter weight [1, 2]. Low weight and smaller size comes about because operation is significantly at a higher frequency range, and thus the magnetic components are quite smaller in size and weight [3]. High switching frequencies in turn results in large switching losses and stresses in power device because during the turn-on and turn-off transients the power device has to withstand high voltage and current simultaneously [4, 5]. Large 𝑑𝑖/𝑑𝑡 and 𝑑𝑣/𝑑𝑡 transitions also induces significant amount of electromagnetic interference (EMI) in the circuit which in turn pollute the utility systems [6]. This problem, if left unattended, may result in lower efficiency and larger size of converters owing to increased size of the heat sinks and EMI filters. Efforts are made in order to alleviate the aforementioned limitations and to enable operation at still higher frequencies while maintaining better conversion efficiency [7].

Snubbers are an essential part of power electronic systems. They are small network of passive components which forms a part of power switching circuits to reduce switching losses and stresses in power devices [8]. But, as the switching losses in the main switch are dissipated in form of heat in snubber resistors, the overall efficiency of the converter is deteriorated. Various soft switching techniques have been proposed in the literature [1, 9, 10] to obtain soft switching of power devices while at the same time maintaining higher overall efficiency. But this is achieved at the cost of increased design complexity of power and control circuits and thereby increasing circuit cost and deteriorating the system reliability [5].

Energy recovery snubber poses a solution to the problem as it is simpler, reliable, and cheaper than most of the soft switching techniques and also helps in reducing the switching losses without deteriorating the overall system efficiency. The energy stored in an energy recovery snubber is either moved back to the input or ahead to the output in a nondissipative manner [5, 6, 8, 11, 12]. Energy recovery snubbers can be further classified as turn-on, turn-off, and combined function snubbers. Turn-on snubbers are basically nondissipative current snubbers which control the rate of rise of current in the main switch at turn-on transient and thereby achieving zero current switching (ZCS) at turn-on transient of the switch [8, 13], while turn-off snubbers are nondissipative voltage snubbers which control growth rate of voltage across the switch during turn-off transient and thus help in achieving zero voltage switching (ZVS) at turn-off transient [8, 14–17]. The combined function snubber, also called as turn-on and turn-off snubber, serves the dual function of achieving ZCS turn-on and ZVS turn-off of the switch during turn-on and turn-off transients, respectively, and hence includes the functionality of both turn-on and turn-off snubber in a single circuit [5]. An energy recovery turn-on and turn-off snubber is thus selected for further investigation and implementation in a high power dc-dc converter.

Although, synthesis and optimization of various snubbers have been widely reported in the literature for low power dc-dc converters [1, 5, 6, 9–19], the issues related to design, optimization, application, and practical aspects pertaining to their use in high power dc-dc converters are not reported. This paper presents the design and optimization of energy recovery snubber with wide operating range for high power dc-dc converters. The presented work is based on the analytical results reported in [5]. Brief operation of the energy recovery snubber is presented in Section 2 followed by design parameters of dc-dc converter in Section 3, design and optimization of energy recovery snubber in Section 4, simulation and experimental results in Section 5, and conclusions in Section 6.

2. Operation of Energy Recovery Snubber

Snubber shown in Figure 1 is an energy recovery turn-on plus turn-off snubber also called as 3D-2C-1L snubber. The snubber network has been called so because it has three diodes, two capacitors, and one inductor. Growth rate of reverse recovery current is controlled by snubber inductor 𝐿_𝑠, while growth rate of voltage across switch is controlled by snubber capacitor 𝐶_𝑠. Energy recovery is achieved by discharging the buffer capacitor 𝐶_𝑏 to the output. The key waveforms of the buck converter with energy recovery snubber are shown in Figure 2 [5]. During turn-on process, the diode recovery current is the major cause of the switching losses and EMI. The rate of rise of current and peak reverse recovery current is restricted by the snubber inductor 𝐿_𝑠 to suppress the switching loss. During turn-off process, the rate of rise of drain-source voltage is restricted by the snubber capacitor 𝐶_𝑠 to obtain ZVS turn off and to reduce EMI noises.

Figure 1 

Buck converter with energy recovery snubber.

Figure 2 

Key waveforms of the buck converter with energy recovery snubber.

The freewheeling diode is also commutated with ZVS during both turn-on and turn-off. The energy absorbed in snubber inductor 𝐿_𝑠 and snubber capacitor 𝐶_𝑠 is transferred to 𝐶_𝑏 instead of being dissipated, which is subsequently transferred to the output. Detailed operation of this snubber with various modes of operation is given in [5].

3. Design Parameters of DC-DC Converter

A high-power prototype of buck converter with maximum output voltage and current ratings of 450 V and 55.5 A, respectively, has been developed to experimentally validate the theoretical design of energy recovery snubber. The design parameters of the buck converter are given in Table 1.

Table 1 

Prototype specifications.

The insulated gate bipolar transistor (IGBT) module used in the prototype is SKM100GAR123D [20].

4. Design and Optimization of Energy Recovery Snubber

Design and optimization of energy recovery snubber are described in six steps as given below. Subsequently, a design flow diagram for snubber parameters calculation is also presented in Figure 3.

Figure 3 

Design flow diagram for snubber parameters calculation.

Step 1 (Choice of 𝐶_𝑠). The snubber capacitor 𝐶_𝑠 shown in Figure 1 is mainly responsible for ZVS turn-off of switch 𝑆₁. Thus, the discharging time of 𝐶_𝑠 should be quite larger than the fall time 𝑡_𝑓 of the switch to ensure proper ZVS turn-off of the switch. When the switch 𝑆₁ turns off, the output current 𝐼_𝑜 flows through 𝐷₂ to discharge 𝐶_𝑠 to the output. During this period, capacitor discharges linearly. If the time taken by 𝐶_𝑠 to discharge completely from the value of 𝑉_𝑑 to zero is 𝑡_𝑑, then, capacitance 𝐶_𝑠 can be written in terms of output current 𝐼_𝑜, input dc voltage 𝑉_𝑑 and discharge time 𝑡_𝑑 as follows: 𝐶_𝑠=𝐼_𝑜𝑡_𝑑𝑉_𝑑. (1)
As typically the fall time 𝑡_𝑓 of the switch is around 100 ns. Thus, to ensure proper ZVS turn-off of the switch, discharge time 𝑡_𝑑 is taken to be approximately five-times the fall time of switch 𝑡_𝑓, that is, 500 ns. Therefore, for (𝐼_𝑜)_max = 55.55 A, (𝑉_𝑑)_min= 504 V, and 𝑡_𝑑=500 ns, the value of snubber capacitance 𝐶_𝑠 comes out to be 0.055 μF from (1). The nearest available value of snubber capacitance used in the practical circuit is 0.047 μF.

Step 2 (Choice of 𝐿_𝑠). When the switch 𝑆₁ shown in Figure 1 is turned on, the growth rate of the drain current is restricted by the snubber inductor to softly turn on the switch. During this duration, rate of fall of main diode current 𝑖_𝐷1, which is also equal to the rate of rise of switch current, is given as follows: 𝑑𝑖_𝐷1=𝑉𝑑𝑡𝐿^𝑑_𝑠. (2)
Values of 𝑑𝑖_𝐷1/𝑑𝑡 calculated for various values of 𝐿_𝑠 and 𝑉_𝑑=600 V using (2) have been listed in column 2 in Table 2. Column 3 in Table 2 shows the estimated values of reverse recovery current 𝐼_rr flowing through main diode 𝐷₁ for the corresponding values of 𝑑𝑖_𝐷1/𝑑𝑡 listed in column 2. These values have been estimated from 𝐼_rr v/s 𝑑𝑖_𝐷𝑓/𝑑𝑡 curve given in the datasheet of IGBT module [20].

Table 2 

Calculation of snubber parameters.

Step 3 (Choice of 𝐶_𝑏). Buffer capacitance 𝐶_𝑏 is expressed in terms of 𝐿_𝑠, 𝐶_𝑠, 𝑉_𝑑, 𝐼_rr, and 𝑉_{𝐶𝑏,𝑝} as follows [5]: 𝐶_𝑏=𝐿_𝑠𝐼_rr²+𝐶_𝑠𝑉_𝑑²𝑉²_{𝐶𝑏,𝑝}. (3)
As the voltage stress of freewheeling diode 𝐷₁ is equal to 𝑉_𝑑 plus 𝑉_{𝐶𝑏,𝑝}, thus the peak voltage appearing across buffer capacitor 𝐶_𝑏 is capped at 235 V to keep the voltage rating of 𝐷₁ within limits (maximum voltage rating of diode 𝐷₁is 1200 V). Hence, the peak voltage appearing across diode 𝐷₁ is given by. 𝑉_𝐷1,𝑝=𝑉_𝑑+𝑉_{𝐶𝑏,𝑝}≅850V. (4)
Thus, values of 𝐶_𝑏 calculated for corresponding values of 𝐿_𝑠, 𝐶_𝑠, 𝑉_𝑑, 𝐼_rr, and 𝑉_{𝐶𝑏,𝑝} are listed in column 4 in Table 2.

Step 4 (Checking for Condition). The necessary condition which ensures the proper ZCS turn-on and ZVS turn-off operation of circuit is given in [5] and can also be written as follows: 12𝐿_𝑠𝐼_𝑜²−12𝐿_𝑠𝐼_rr²−12𝐶_𝑠𝑉_𝑑²<0. (5)
Column 5 in Table 2 calculates the left hand side (LHS) of inequality given in (5) and the result is 𝑇𝑅𝑈𝐸 if LHS is negative, while 𝐹𝐴𝐿𝑆𝐸 otherwise.

Step 5 (Check for 𝐷_min and 𝐷_max). Maximum and minimum duty cycle limits are imposed on the buck converter due to finite time taken by the snubber circuit for its operation. During this duration, the normal operation of buck converter is suspended. Maximum duty cycle limit occurs due to the snubber circuit operation at switch turn-off transition, while minimum duty cycle limit occurs due to the snubber circuit operation at switch turn-on transition. Thus, the duty cycle limits can be obtained by calculating the time taken by the snubber both during turn-on and turn-off transitions.
Various stages of operations have been discussed in [5]. Out of 8 stages of operation of buck converter circuit described in [5], snubber is active during 6 stages (𝑡₀<𝑡<𝑡₁),(𝑡₁<𝑡<𝑡₂), (𝑡₂<𝑡<𝑡₃), (𝑡₄<𝑡<𝑡₅), (𝑡₅<𝑡<𝑡₆), and (𝑡₆<𝑡<𝑡₇). Time duration of all these 6 stages are calculated here for values of 𝐿_𝑠 varying from 1 μH to 10 μH, 𝐶_𝑠=0.047 μF, 𝑉_𝑑=600 V, peak voltage across buffer capacitor 𝑉_{𝐶𝑏,𝑝}=235 V, and output current 𝐼_𝑜=56 A. To do this, expressions for time durations for these stages are derived based on equations describing voltages and currents given in [5]. They are summarized as follows.
Time duration 𝑇_𝑑1 of stage 1 is given by 𝑇_𝑑1=𝑡₁−𝑡₀=𝐿_𝑠𝑉_𝑑𝐼_𝑜+𝐼_rr. (6)
Time duration 𝑇_𝑑2 of stage 2 is given by 𝑇_𝑑2=𝑡₂−𝑡₁=1𝜔₁sin⁻¹𝐶_𝑠𝑉_𝑑𝐶_𝑏𝐼_rr𝑍₁²+𝑉_𝑑²+tan⁻¹𝑉_𝑑𝐼_rr𝑍₁, (7) where 𝑍₁ and 𝜔₁ are given in (8), 𝑍₁=𝐿_𝑠𝐶_𝑠+𝐶_𝑏𝐶_𝑠𝐶_𝑏,𝜔₁=𝐶_𝑠+𝐶_𝑏𝐿_𝑠𝐶_𝑠𝐶_𝑏. (8)
Time duration 𝑇_𝑑3 of stage 3 is given by 𝑇_𝑑3=𝑡₃−𝑡₂=1𝜔₂tan⁻¹𝐶_𝑏𝐼_𝑠2𝑍₂𝐶_𝑠𝑉_𝑑, (9) where 𝐼_𝑠2, 𝑍₂ and 𝜔₂ are given by (10), and (11), respectively: 𝐼_𝑠2=𝑉_𝑑𝑍₁sin𝜔₁𝑇_𝑑2+𝐼_rrcos𝜔₁𝑇_𝑑2,𝑍₂=𝐿_𝑠𝐶_𝑏,𝜔₂=1𝐿_𝑠𝐶_𝑏. (10)(11)
Time duration 𝑇_𝑑4 of stage 5 is given by 𝑇_𝑑4=𝑡₅−𝑡₄=𝐶_𝑠𝑉_𝑑𝐼_𝑜. (12)
Time duration 𝑇_𝑑5 of stage 6 is given by 𝑇_𝑑5=𝑡₆−𝑡₅=1𝜔₂sin⁻¹𝐼_𝑜𝑍₂𝑉_{𝐶𝑏,𝑝}. (13)
Time duration 𝑇_𝑑6 of stage 7 is given by 𝑇_𝑑6=𝑡₇−𝑡₆=𝐶_𝑠𝑉_𝑑𝐼_𝑜cos𝜔₂𝑇_𝑑5, (14) where 𝑇_𝑑5 is given by (13).
The switch 𝑆₁ must be on from 𝑡=𝑡₀ at least till 𝑡=𝑡₃ when 𝐼_𝐿𝑠 becomes zero. This governs the minimum duty cycle limit which is given by Minimumdutycyclelimit𝐷_min=𝑇_𝑑1+𝑇_𝑑2+𝑇_𝑑3𝑇_𝑠, (15) where 𝑇_𝑑1,𝑇_𝑑2, and 𝑇_𝑑3 are given by (6), (7), and (9) respectively, and 𝑇_𝑠 is the switching time period. Values of minimum duty cycle limit calculated for 𝑇_𝑠=40 μs, corresponding to the switching frequency of 25 kHz are listed in column 7 in Table 2.
The switch 𝑆₁ must be maintained in off condition from 𝑡=𝑡₄ to at least 𝑡=𝑡₇ when the buffer capacitor 𝐶_𝑏 is discharged completely. This dictates maximum duty cycle limit given by Maximumdutycyclelimit𝐷_max𝑇=1−^𝑑4+𝑇_𝑑5+𝑇_𝑑6𝑇_𝑠. (16)

Step 6 (Calculation for Ratings). Peak value of the drain current of switch 𝑆₁ appears when 𝑉_𝐶𝑏+𝑉_𝐶𝑠 becomes equal to 𝑉_𝑑 and is obtained by the summation of output current 𝐼_𝑜 and peak snubber inductor current 𝐼_{𝐿𝑠,𝑝} which is given by [5]: 𝐼_{𝐿𝑠,𝑝}=𝑉_𝑑²+𝐼_rr𝑍₁²𝑍₁, (17) where, 𝑍₁=𝐿_𝑠𝐶_𝑠+𝐶_𝑏𝐶_𝑠𝐶_𝑏. (18)
Thus, peak switch current is given by 𝐼_sw,𝑝=𝐼_𝑜+𝐼_{𝐿𝑠,𝑝}. (19)
Therefore, from (17), (18), and (19), peak value of switch current 𝐼_sw,𝑝 is calculated for corresponding values of 𝐿_𝑠, 𝐶_𝑠, 𝐶_𝑏,𝑉_𝑑, 𝐼_rr, and 𝐼_𝑜 and listed in column 6 in Table 2.
For the buck converter prototype, specifications of which are given in Table 1, iterative calculations have been done for buffer capacitance of snubber 𝐶_𝑏, peak current rating of switch 𝐼_sw,pk, and minimum and maximum duty cycle limits for various values of snubber inductance 𝐿_𝑠 ranging from 1 μH to 10 μH while taking 𝐶_𝑠=0.047 μF, 𝑉_𝑑=600 V, peak voltage across buffer capacitor 𝑉_{𝐶𝑏,𝑝}=235 V, and output current 𝐼_𝑜=56 A as shown in Table 2. Highlighted values in the table show the selected snubber parameters.𝐼_rr shown in table is the estimated reverse recovery current of the main diode 𝐷₁.
Values of maximum duty cycle limit calculated for 𝑇_𝑠=40 μs are listed in column 8 in Table 2. It is important to note that the choice of snubber components, therefore, also governs the operating range of the converter in addition to various voltage and current stresses described previously.
Snubber parameters, therefore, should be selected after making a tradeoff between the maximum permissible switch current rating, diode voltage rating, and operating duty cycle range provided that the circuit satisfies the inequality given in (5) which ensures proper soft switching operation of snubber over that range.
Based on the calculations illustrated in Table 2, the following component values are chosen: 𝐿_𝑠=4 μH, 𝐶_𝑠=0.047 μF, 𝐶_𝑏=0.33 μF, 𝐼_sw,𝑝=119.45 A, 𝑉_𝐷1,𝑝=850 V, 𝑉_{𝐶𝑠,𝑝}=616 V, 𝐼_{𝐶𝑠,𝑝}=55.5 A, and 𝑉_{𝐶𝑏,𝑝}=235 V, 𝐼_{𝐶𝑏,𝑝} = 55.5 A.
Diodes APT60D100B are used for snubber diodes [21]. Inductor 𝐿_𝑠 is developed in EE65.32.18 core with 4 turns and an air gap of 1.4 mm.

5. Simulation and Experimental Results

Simulation results for voltage and current waveforms across switch in the presence of energy recovery snubber are shown in Figures 4 and 5, respectively, during on-time and off-time transitions for input dc voltage, 𝑉_𝑑=616 V and output current, 𝐼_𝑜=56 A. From Figures 4 and 5, respectively, it is observed that energy recovery snubber helps in achieving ZCS turn-on and ZVS turn-off of switch 𝑆₁ at turn-on and turn-off transients.

Figure 4 

ZCS turn-on of switch 𝑆1.

Figure 5 

ZVS turn-off of switch 𝑆1.

Simulation results for comparison of efficiency of buck converter with and without dissipative and nondissipative snubbers are shown in Figure 6 in which 𝑥-axis represents duty cycle variation from 0.1 to 0.9, while 𝑦-axis represents efficiency of buck converter. Dissipative snubber used in simulation consists of two cells one of which is responsible for achieving ZCS turn-on of the switch, while the other one ensures its ZVS turn-off. The turn-on snubber cell is placed in series with the switch and consists of an inductor (4 μH) connected in parallel with the series combination of a resistor (5 Ω) and an ideal diode. While the turn-off snubber cell is placed across the switch and consists of a capacitor (0.047 μF) placed in series with a parallel combination of a resistor (68 Ω) and an ideal diode. Nondissipative snubber components used in simulation are same as summarized in Section 4. From Figure 6 it is observed that efficiency of the buck converter reduces when a dissipative snubber is used to limit the switching losses. This is because of the fact that in dissipative snubbers switching losses in power devices are transferred to the dissipative component in the snubber thereby reducing overall efficiency of the converter. But, in contrast to this, nondissipative snubber reduces the switching losses by temporarily storing the energy of one switching transient in a buffer and then transferring it either back to the input or ahead to the output during the next switching transient in a nondissipative manner and thereby, reducing the switching losses while at the same time increasing the efficiency of the converter. The improvement in efficiency with energy recovery snubber is evident in simulation waveforms of Figure 6.

Figure 6 

Efficiency comparison of buck converter with dissipative and nondissipative snubbers.

The simulation waveforms shown in Figures 4 and 5 are valid only for ideal circuits which are free of any wiring inductances. But, in practical circuits, these wiring inductances play a significant role in introducing undesirable effects on the circuit operation. This can be demonstrated by introducing some wiring inductance in series with the input dc supply of simulation circuit. Figure 7 shows the simulation waveforms with the effects of wiring inductance of 100 nH introduced in the simulation circuit.

(a)

(b)

(c)

(d)

Figure 7 

Simulation waveforms with effect of wiring inductance for 𝐷=0.5, 𝑉𝑑=616 V, and 𝐼𝑜=56 A: gate pulses, voltage and current in 𝑆1, voltage and current in 𝐷1, and current in 𝐿𝑠.

From Figure 7, it is observed that the wiring inductances have significant undesirable effect on the circuit performance. During turn-off transition, ringing is observed in switch voltage and current waveforms which results in an overlap between the two during the transition interval and thereby resulting in switching loss at turn-off transition as shown in Figure 7. Ringing is also observed in switch current after turn-on transition which disrupts the normal functioning of the buck converter during this interval as shown in Figure 7. Thus, significant steps should be taken during the development phase of the converter to minimize these wiring inductances by making a judicious arrangement for the assembly of snubber and other components of the converter. This can be done by prudently placing the components containing high frequency currents as close to each other as possible and thereby minimizing the wiring length which in turn results in reduced wiring inductance. Another way to reduce wiring inductance is to use twisted cables or to use flat wide conductors and using copper strips.

Figures 8(a) and 8(b) shows the experimental waveforms of the voltage across the switch (𝑣_𝑠1) and current through it (𝑖_𝑠1) at turn on and turn off transitions, respectively, for 𝐷=0.5 and 𝑉_𝑑=200 V. From Figure 8, it is clear that the switch turns on under ZCS condition and turns off under ZVS condition which is in agreement with the theoretical analysis of switch voltage and current waveforms and also with the simulation results presented in Figure 7.

(a)

(b)

Figure 8 

Experimental waveforms of 𝑣𝑠1 (50 V/div) and 𝑖𝑠1 (10 A/div) at (a) turn-on transition and (b) turn-off transition. In both parts, Ch3 shows gate pulse for switches (𝑣𝑔𝑒−𝑠1, 20 V/div) and XScale is 250 ns/div.

Figures 9(a) and 9(b) shows the experimental waveforms of main diode 𝐷₁ voltage(𝑣_𝐷1)and snubber inductor 𝐿_𝑠 current (𝑖_𝐿𝑠) at turn on and turn off transitions respectively for 𝐷=0.5 and 𝑉_𝑑=200 V.

(a)

(b)

Figure 9 

Experimental waveforms of 𝑣𝐷1 (50 V/div) and 𝑖𝐿𝑠 (10 A/div) at (a) diode turn-on transition and (b) diode turn-off transition. In both parts, Ch3 shows gate pulse for switches (𝑣𝑔𝑒−𝑠1, 20 V/div) and XScale is 500 ns/div.

Since snubber inductor 𝐿_𝑠 is connected in series with the main diode 𝐷₁, as shown in Figure 1, a part of snubber inductor current flows through main diode 𝐷₁ both during turn-on and turn-off transitions. As, it is difficult to monitor current waveform in main diode, snubber inductor current is observed here to demonstrate the ZVS turn-on and ZVS turn-off of the main diode 𝐷₁. From Figure 9, it is clear that the main diode 𝐷₁ also turns-on and turns-off under ZVS condition which is in agreement with the theoretical analysis of main diode voltage and current waveforms and also with the simulation results presented in Figure 7.

Figure 10(a) shows the snubber inductor 𝐿_𝑠 current waveform for full cycle of operation while Figure 10(b) shows the voltage and current waveforms of main diode 𝐷₁ and output filter inductor 𝐿_𝑚, as shown in Figure 1, respectively for 𝐷=0.5 and 𝑉_𝑑=200 V. Figure 10(a) demonstrates that the snubber inductor current waveform is in accordance with the theoretical analysis and also with the simulation results presented in Figure 7. While Figure 10(b) shows that the voltage and current waveforms respectively of 𝐷₁ and 𝐿_𝑚 are in agreement with the theoretical analysis of basic buck converter circuit.

(a)

(b)

Figure 10 

Experimental waveforms of (a) 𝑖𝐿𝑠 (10 A/div) with XScale of 5 μs/div and (b) 𝑣𝐷1(50 V/div), 𝑖𝐿𝑚(5 A/div) with XScale of 10 μs/div. In both parts, Ch3 shows gate pulse for switches (𝑣𝑔𝑒−𝑠1, 20 V/div).

Figure 11 shows the graph for efficiency comparison of buck converter with and without nondissipative snubber. Graph is plotted for input dc voltage of 100 V because full load operation of circuit could be detrimental for the devices in absence of snubber. It is quite clear from this graph that the efficiency of buck converter improves by using nondissipative snubber in the circuit, which is also in agreement with the simulation result as shown in Figure 6.

Figure 11 

Measured efficiency of buck converter with and without nondissipative snubber at 𝑉𝑑=100 V.

6. Conclusions

Snubbers are essential part of switching power electronic circuits as these helps in reducing switching losses, stresses on semiconductor devices as well as EMI. Various types of soft switching snubbers are available in literature out of which an energy recovery snubber is selected for high power dc-dc step-down converter owing to its distinct advantages over other types. For high power applications, optimization of snubber parameters is done by making a tradeoff between the maximum permissible switch current rating, diode voltage rating and operating duty cycle range provided that the circuit satisfies an inequality which ensures proper soft switching operation of snubber over that duty cycle range. As wiring inductance brings about undesirable effects in the circuit operation, efforts should be made to minimize the wiring inductance by judicious selection of circuit layout. Experimental waveforms shows that the energy recovery snubber helps in reducing switching losses as well EMI by achieving ZCS turn-on and ZVS turn-off of switch 𝑆₁ and also ZVS turn-on and turn-off of diode 𝐷₁ without deteriorating overall efficiency of the converter. Practical effects of the wiring inductance on circuit performance are also demonstrated by experimental waveforms.