Research Article  Open Access
An IFOCDSVPWM Based DCLink Voltage Compensation of ZSource Inverter Fed Induction Motor Drive for EVs
Abstract
The drop in DClink voltage of adjustable speed drives (ASD) occurs mainly due to the increase in output power demands. This may lead to inefficient operation and eventually the tripping of the drive. This paper presents a Double Space Vector Pulse Width Modulation (DSVPWM) technique for boosting and compensating the DClink voltage of Zsource inverter (ZSI). The DSVPWM technique estimates the required shoot through period of the Zsource inverter to maintain the DClink voltage constant at the desired level through capacitor voltage control. The DSVPWM can obtain maximum boost at any given modulation index in comparison to simple boost control (SBC) method. It also utilizes the dead time more effectively. The speed control of the ZSI fed induction motor drive is done by employing indirect fieldoriented (IFO) control method. A 32bit DSP (TMS320F28335) is used to implement the IFOCDSVPWM method for ZSI. The power structure and the modulation technique are well suited for electric vehicle application.
1. Introduction
Why electric vehicles? The world population and vehicles are increasing rapidly. In the next 100 years, the growth of the world population will be from 7 to 15 billion and the number of vehicles may increase from 0.7 to 3 billion. If all these vehicles are propelled by internal combustion engines (ICEs), where will the oil come from? Where should the emissions be accommodated? The need of the hour is emissionfree road transportation for the 21st century.
In the world where environmental protection and energy conservation are growing concerns, the development of EV technology will achieve these demands. The EVs can provide emissionfree urban transportation. In the energy aspect, EVs can offer a secure and balanced energy from various kinds of the renewable energies. Therefore, EVs will have a great impact on energy, environment, transportation, new industry creation, and economic development [1, 2].
The main components of the EV are (i) battery as an electrical energy source, (ii) a power converter which controls electrical energy, (iii) an electrical motor as an electromechanical conversion device for traction, and (iv) a central DSP or microcontroller as a control system for the power converter. Selection of electrical (traction) motors for propulsion systems is a very important step that requires special attention. In fact, the automotive industry is still seeking for the most appropriate electric propulsion system for EV. In this case, key issues are efficiency, torque density, weight, cost, cooling, maximum speed, faulttolerance, safety, and reliability. The types of electric motors adapted for electric vehicles are DC motor, the induction motor, the permanent magnet synchronous motor, and the switched reluctance motor. Of late, the cage induction motors are accepted as the most suitable motors for the electric propulsion of EVs owing to their reliability, ruggedness, low maintenance, low cost, and ability to operate in inimical environments. They are particularly well suited for industrial and traction drive environments. Today, induction motor drive is the most mature technology among various commutatorless motor drives. The high performance control of induction motors can decouple its torque and field control [3, 4].
In a voltage source inverter fed induction motor for an EV, the speed control techniques are scalar control (), indirect fieldoriented control (IFOC), and direct torque control (DTC). For low price applications, the volts per hertz induction motor drives with voltage source inverters are widely used in industry. The main advantage of the control is its simplicity, but its accuracy is low and its torque response is poor. For those applications which require better dynamic performance, the indirect fieldoriented control (IFOC) or the direct torque control is preferred. These methods have several common aspects, such as the decoupled control of motor flux and torque, fast torque response, and sensitivity to certain motor parameters. The flux command in conventional IFOC is the directaxis rotor flux in the synchronous frame, while that of DTC is the stator flux in the synchronous frame. IFOC avoids the need for a flux estimator. References [5–7] conclude that IFOCSVPWM performs well comparable to the DTCSVPWM.
The electric drive employs a DCDC boost converter for boosting the low voltage of a battery for the DCAC inverter. The problem in adding a boost converter is that it increases the cost and lowers the efficiency and reliability of the system. When the load on a drive is suddenly increased, the DCbus voltage experiences drop. This voltage drop can be so much to an extent that it could lead to a loss of power delivery to the load. So, this voltage drop has to be compensated for better reliability. In addition to this, the dead time with which the inverter is operated to ensure safety distorts the output voltage waveform. A combined solution for voltage drop compensation and minimization of output voltage distortion is impedance or Zsource inverter. This will be dealt with in detail in a subsequent section. A Zsource inverter has a Znetwork between the DC electrical source and the inverter. The capacitor voltage of the Znetwork acts as a DClink for the inverter. ZSI intentionally avoids the dead time and creates a shootthrough to boost the capacitor voltage in the Znetwork which in turn compensates the voltage drop.
The proposed DSVPWM method can achieve the maximum boost at any given modulation index and with better DClink voltage utilization is achieved compared to SBC method. The organization of the paper is as follows. Section 2 describes the small signal analysis and components design of the Zsource inverter. Section 3 describes the DSVPWM boost technique. Section 4 describes the DClink voltage control through capacitor control. Section 5 describes speed control of induction motor. Section 6 inculcates hardware implementation of VSI and ZSI drive, the results discussion.
2. ZSource Inverter
The operational problems associated with voltage source and current source inverters led to the development of Zsource inverter. As shown in Figure 1, a Znetwork is inserted between DC source and 3 legs of inverter switches. The DC source can be battery, diode rectifier, fuel cell, and so forth. The apparent features of Zsource system are as follows [8].(i)Znetwork is a secondorder filter, which is more effective in suppressing voltage ripples than capacitor filter used in the traditional PWM inverters.(ii)The inductor limits the inrush current and current harmonics.(iii)Znetwork provides boosting in voltage across the DClink.(iv)The shootthrough state facilitates boosting in output voltage, instead of damage to the power circuit.
2.1. Small Signal Model
In view of complete understanding of dynamic response of the system, it is necessary to have state space averaged smallsignal model of the converter.
The ZSI equivalent circuit is shown in Figure 2. The small signal modeling begins with the following assumptions: (i) the passive components in the Znetwork are lossless; (ii) the load current is continuous; and (iii) the input voltage is an independent voltage source. The capacitor voltage , the inductor current , and the load current are the state variables and they operate in two modes [9, 10].
Mode 1. Inverter circuit as shown in Figure 3(a) is operating in one of the six active states and the circuit can be seen as an equivalent current source. During this mode, the DC source voltage appears across the inductor and the capacitor. The power transfers from the source to the load through inductor.
(a)
(b)
Mode 2. Inverter circuit as shown in Figure 3(b) is operating in one of the seven different ways of shootthrough state. The inverter circuit looks like a “short circuit” from the DClink of the inverter and in shootthrough state, the capacitor voltage becomes higher than the input DC voltage, which makes the diode reversebiased. The voltage does not appear across the load like in the zero state.
During this mode, there is no power transfer from the source to the load because the load and source sides are decoupled by the shootthrough state and the open switch . The standard state space equations are written in matrix form using state space averaging method and performing small signal perturbation for a given operating point [11–14] (linearising the system) as follows:
Znetwork inductor and capacitor ,
From Laplace transformation of (1),
Use the following relationships for the capacitor voltage and inductor current [15]:The DClink voltage is pulsating due to shootthrough state. The DClink voltage peak value during the nonshootthrough state is and during shootthrough state is zero. Therefore, the perturbation in the DClink voltage has been written as
From small single modeling, the capacitor voltage, the inductor current, and the DClink voltage can be expressed as a linear combination of the variable response to each individual perturbation aswhere , , , , , and are individual transfer functions.
2.2. ZNetwork Components Design
Mode 1. During nonshootthrough condition, inductor voltage is different from capacitor voltage and inductor current decreases linearly.
Mode 2. Capacitor and inductor voltage become equal and inductor current increases linearly [16].
So the average current through inductor can be written aswhere is converter power rating and is input DC source voltage.
When the shootthrough period is maximum, the current ripple through the inductors becomes maximum. For the design of inductor, inductor current ripple is considered as 50% of the inductor current: Max. inductor current ; Min. inductor current .
In ZSI [15],
; is the shootthrough period per switching cycle.
From (7), (8), and (9), capacitor voltage can be expressed asor During shootthrough,
Inductor value is where .
Restricting the capacitor voltage ripple () to less than 1%, the capacitor value can be calculated as
The designed/calculated values of Znetwork are given in the appendix.
3. PWM Technique
In inverters, there are many PWM techniques in use. Sinusoidal Pulse Width Modulation (SPWM) technique is the most basic technique in practical applications. The Space Vector Pulse Width Modulation (SVPWM) is an advanced computationintensive PWM technique, preferred in realtime realization, being widely used in voltage source inverters. This technique generates reference threephase signals by sharing the space vector among the active and zero vectors such that the harmonic content is optimized. The maximum inverter linetoline voltage generated by the SVPWM scheme is 15.5% higher than that of the SPWM for a given DC bus voltage [17, 18].
In SVPWM technique for VSI, eight switching states (six active + two zero/null) are realised. During the six active states, the supply is connected to the load and during the two zero/null states, the load terminals are shortened by the switching devices. In the ZSI, an extra state called shootthrough state is realised during which upper and lower switching devices of the same leg are turned on [19]. This state is forbidden in traditional VSI as it leads to supply short circuit and results in high and devicedamaging surge current. In ZSI, the advantage of having Znetwork between the supply and the inverter switches is that the rise in the shootthrough state current is limited by the inductor of the Znetwork. In addition to this, the inductor in Znetwork stores energy during this state to boost the capacitor voltage and helps in regulating it. This shootthrough state sometimes also called the third zero state is generated in seven different ways: shootthrough via any phase, combinations of any twophase legs, and all threephase legs. Its duration can be adjusted/controlled for different output voltage gain by different boost control methods.
In the Simple Boost Control (SBC) method [15], the resulting voltage stress across the switches is higher as some portion of traditional zero states is not utilized. The Double Space Vector Pulse Width Modulation (DSVPWM) technique uses two sets of threephase signals as reference signals and a high frequency triangular wave as carrier signal [20]. Let , , and be the first set of reference signals generated by SVPWM technique for required modulation “” of input voltage. Let , , and be the second set of reference signals generated by adding a finite negative DC offset () to the first set. The reference signals and will generate pulse for top switch and bottom switch of leg “,” respectively, as shown in Figure 4. The offset results in a shootthrough time per switching period in that leg. For high switching frequencies, the reference signals and can be approximated as constant during a switching cycle. The relation between the shootthrough time and can be established as follows: In Figure 5, consider similar triangles “” and “”:Shootthrough time of leg is
The shootthrough time in all three legs of the inverter remains the same whereas the instants at which they occur during a switching period vary. So, the shootthrough time in legs and is The total shootthrough time per switching period can be written as
The shootthrough duty ratio can be defined as
The DSVPWM technique introduces to extend the pulse width of the bottom switch into the top switch pulse width to result in shootthrough time. When the ZSI is operated at a SVPWM modulation index of “,” the minimum pulsewidth of the top switch is and it occurs in a switching period during the negative halfcycle of the fundamental wave. The bottom switch pulse width during this switching period is when is zero. As increases, the bottom switch pulse width increases from to a maximum of at a maximum offset voltage . On further increase in , SVPWM operation enters overmodulation region. So, the maximum limit can be obtained as follows.
At maximum offset voltage condition, if is the maximum shootthrough time of leg ,
From (15),
Substituting in (22),
From (19) and (25), the maximum shootthrough duty ratio is
From (9) and (26), the maximum boost factor is
For SBC control method, the maximum boosting factor that can be obtained is
A comparison among SBC and DSVPWM boost control methods for maximum boosting factor variation with modulation index using (27) and (28) is shown in Figure 6. The advantage of DSVPWM technique is that the maximum boosting factor is higher than that of SBC boost control method.
The overall voltage gain of the ZSI using DSVPWM is given aswhere is the peak of the fundamental component of phase voltage and is the input DC source voltage.
Modulation index “” of SVPWM technique is defined as
Substituting Znetwork boost factor definition from (9) and shootthrough duty ratio from (18) in (29), we get
Table 1 and Figure 7 show variation in the capacitor voltage with the shootthrough time “” and modulation index “” for the input voltage of 50 V and switching frequency of 10 kHz.

(a)
(b)
(c)
4. DCLink Voltage Control
The DClink voltage control is worked out for a ZSI fed induction motor drive realizing IFOC along with DSVPWM technique for the required voltage compensation. A change in load or speed effects the DClink voltage. It is a pulsating value and its control is difficult. So, the DClink voltage is indirectly controlled by employing the capacitor voltage control. The capacitor voltage control block diagram is shown in Figure 8. The reference capacitor voltage is obtained from the reference DClink voltage and input voltage using (4). The error in actual and reference capacitor voltage is fed to a PI controller to obtain the appropriate value. This value is used to generate the two sets of reference signals as mentioned in DSVPWM technique. The gating pulses obtained from the DSVPWM technique result in both required modulation index and shootthrough duty ratio . The shootthrough duty ratio calculator uses (19) to calculate from the value obtained from the PI controller. It is necessary to establish capacitor voltage to shootthrough duty ratio plant transfer function to tune the PI controller for total voltage drop compensation.
The capacitor voltagetoshootthrough duty ratio plant transfer function is expressed as follows [9]:where , , , , , , and .
Using ZSI parameters in Table 2, induction motor parameters in Table 3, and the closed loop system involving , calculator, and transfer function , the PI controller is tuned. The SISO tool MATLAB/Simulink is used for tuning and the settings of the PI are as follows:(i)overshoot less than 10%;(ii)rise time less than 0.01 seconds;(iii)settling time less than 0.05 seconds;(iv)steadystate error less than 1%.The tuned PI controller exhibits a phase margin (PM) and gain margin (GM) of 59.5 deg and 12.3 dB, respectively. This assures the system stability of the designed mathematical model with the abovementioned circuit parameters.


The values of the tuned PI controller are and .
5. Speed Control
5.1. FieldOriented Control
The vector control scheme facilitates an independent control of torque and flux in the induction motor. In this work, rotor fluxoriented scheme has been implemented.
The induction motor in an arbitrary reference frame is expressed by the following equation [21]:where and are the stator and currents; and are the rotor fluxes; is the rotor angular velocity; is the angular speed of the arbitrary reference frame; and are the rotor and mutual inductances, respectively; is the rotor resistance; is the rotor inertia; is an external torque load; is the number of poles; and is the generated torque.
6. Hardware Implementation
This section explains the hardware implementation of the ZSI fed induction motor drive for voltage drop control. The drive is controlled by programming IFOC algorithm with DSVPWM technique on a TMS320F28335 Texas Instruments Microcontroller. The basic technique of a IFO speed control is that the measured and line currents are converted into a complex sparse vector system by Clarke transformation. The space vector is then transformed from the system to the system by a Park transformation where usually the flux angle is used as the transformation angle . The transformation angle is estimated from the current model by using the currents and rotor speed . In this way a fluxoriented system is obtained. For the DCcurrents obtained after the transformations, usually a standard PIregulator together with some feedforward terms is used. The output of the current regulator is the stator voltage space vector, expressed in the system. The stator voltage space vector is then transformed back to the stationary three phase system using inverse Park and inverse Clarke transformations and the obtained phase voltages are used as reference for the PWM pulse generation. At the same time, the input and capacitor voltages are sensed for calculating the DClink voltage. This DClink voltage is regulated using a PI controller, whose output is the shootthrough duty ratio . The DSVPWM pulses with the shootthrough duty ratio is realized using DSVPWM technique by programming the TI microcontroller. The flow chart for DSVPWM technique is shown in Figure 9.
The capacitor voltage , input voltage , motor line currents and , and the rotor speed are sensed and given as feedback signals to the microcontroller shown in Figure 10. The CCS5.4 software with GUI composer from Texas Instruments provides integrated environment for the development of the target application. The IFOC with DSVPWM algorithm is programmed using CCS5.4 software and loaded into the microcontroller. The microcontroller executes the algorithm using the analog inputs to generate gating pulses for the inverter switches with required modulation and shootthrough time for speed and DClink voltage control. The GUI composer scatter plot is utilized to monitor the realtime updating of the variables in the operation of the drive system. Some of the scatter plots obtained are shown as part of results in the latter part of this section. The DClink voltage compensation has been successfully implemented. To evaluate the performance of the ZSI based drive, a VSI based drive has also been implemented.
6.1. VSI Fed Induction Motor Drive
The VSI is connected to a 600 V DC source and feeds a 3.2 kW, 1500 rpm threephase squirrel induction motor. The motor is mechanically coupled to a 220 V, 3.2 kW seperately excited DC generator. The DC generator is loaded with incremental resistive loading. Two cases in which voltage drop takes place have been studied.
Case 1. The VSI fed drive is given a constant speed reference of 750 rpm. The torque, increased from no load to 30% of full load in three equal steps at (10%), (20%), and (30%) instants and decreased from 30% of full load to no load in three equal steps at (20%), (10%), and (no load) instants by changing the loading on the coupled DC generator. The rotor speed is changing from 733 to 765 rpm with load change. The rotor speed performance indices as peak over shoot, rise time, and setting time are 2%, 1 sec, and 2 secs, respectively. The response of rotor speed and input DClink voltage drop are shown in Figures 11(a) and 11(b). It can be observed that the IFOC results in speed control, but the DClink voltage experiences voltage drop.
(a) Induction motor rotor speed
(b) DClink voltage response
Case 2. The VSI fed drive is given fourstep changes in speed reference from 750 rpm to 850 rpm, to 950 rpm, to 850 rpm, and to 750 rpm under loaded condition. The rotor speed performance indices as peak over shoot, rise time, and setting time are 10%, 2.5 secs, and 5 secs, respectively. The motor speed follows the reference speed as shown in Figure 12(a) and the corresponding input DClink voltage drop can be observed in Figure 12(b).
(a) Induction motor rotor speed
(b) DClink voltage response
In both of the above cases of VSI fed drive, voltage drop remains uncompensated. The modulation index of VSI varies to maintain constant rated flux in the motor.
6.2. ZSI Fed Induction Motor Drive with DSVPWM Technique
The ZSI is connected to a 400 V DC source and feeds the induction motorDC generator set previously mentioned. The two cases studied in VSI drive are studied here for comparison.
Case 1. The ZSI fed drive, under constant speed reference 750 rpm and varying load torque, not only maintains the speed but also compensates the DClink voltage to 600 V. The rotor speed is changing from 748 to 752 rpm with load change. The rotor speed performance indices as peak over shoot, rise time, and setting time are 0.26%, 0.1 secs, and 0.3 secs, respectively. Figures 13(a) and 13(b) show the rotor speed , DClink voltage , capacitor voltage , and input voltage response.
(a) Induction motor rotor speed
(b) DClink voltage response
Case 2. The speed reference of ZSI fed drive is changed in four steps as in the case of VSI under loading condition. The motor speed and the DClink voltage are following the speed reference and 600 V, respectively. Figures 14(a) and 14(b) show the rotor speed DClink voltage , capacitor voltage , and input voltage response. The rotor speed performance indices as peak over shoot, rise time, and setting time are 2%, 1 sec, and 1.5 secs, respectively. The above observations from VSI and ZSI drives have been tabulated in Tables 4 and 5.


(a) Induction motor rotor speed
(b) DClink voltage response
In both of the above cases of ZSI fed drive, the DClink voltage is compensated owing to the shootthrough generation by DSVPWM technique used. Based on Table 4, Figure 15 shows the variation in DClink voltage and modulation index in VSI and ZSI fed drives under constant speed and variable load torque mode. The drop in DClink voltage of VSI on increased loading is too large and in ZSI the DClink voltage is maintained constant. Hence, modulation index “” of the VSI increases steeply compared to that in the ZSI fed drive. This is because the Znetwork in ZSI fed drive provides the boost to the DClink voltage, thereby causing less rise in modulation index “.”
Figure 16(a) shows the Znetwork elements inductor and capacitor and IPM inverter module (BSM50GD120DN2E3226) with driver (ADUM4332) circuit which are the main components in Zsource inverter. Figure 16(b) shows the total setup of the Zsource inverter. Figure 16(c) shows 3.5 kW motorgeneration load setup for Zsource inverter and the speed of the motor is measured through the ACtachogenerator. The speed sensor output is sine wave and it is converted into pulses using a zero crossing detector circuit. The pulses are fed through the capture module of the DSP for speed sensing.
(a)
(b)
(c)
7. Conclusion
This paper presents the DSVPWM boost control scheme for the DClink voltage control of Zsource inverter. The proposed DSVPWM based Zsource inverter is capable of compensating voltage drop by generating required shootthrough. A prototype of a 3.5 kW VSI and ZSI fed induction motor drives are designed and implemented with a DSP controller based on the TMS320F28335 evaluation board. The following observations have been made. For load changes, the DSVPWM based ZSI drive shows reduced speed overshoot, rise time, and settling time apart from eliminating the DClink voltage drops as compared to a VSI fed drive. For speed changes, the proposed technique shows reduced speed dips apart from maintaining the DClink voltage stably. This shows that the DSVPWM with ZSI drive has better performance than the VSI drive. This technique greatly improves the voltage boost and utilizes the DClink voltage effectively than classical SBC method.
Appendix
Consider the following: The maximum output power = 3.5 kW. The input DC source voltage = 400 V. The peak DClink voltage = 600 V. Average inductor current is
Max. inductor current
Min. inductor current
.
From (7), boosting factor is
From (9), shootthrough duty ratio
Switching frequency is .
Shootthrough time .
From (10), capacitor voltage is
From (12), inductor value is
Capacitor voltage ripple () is 1%.
From (13), capacitor value is
Conflict of Interests
The authors declare that there is no conflict of interests regarding the publication of this paper.
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Copyright
Copyright © 2015 Ananda Kumar Akkarapaka and Dheerendra Singh. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.