International Journal of Antennas and Propagation

International Journal of Antennas and Propagation / 2011 / Article
Special Issue

Mutual Coupling in Antenna Arrays 2011

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Research Article | Open Access

Volume 2011 |Article ID 540275 | 12 pages |

Spatial Correlation for DoA Characterization Using Von Mises, Cosine, and Gaussian Distributions

Academic Editor: Hoi Shun Lui
Received02 May 2011
Accepted02 Jul 2011
Published08 Sep 2011


This paper presents mathematical expressions for the spatial correlation between elements of linear and circular antenna arrays, considering cosine, Gaussian, and Von Mises distributions, for the direction of arrival (DoA) of the electromagnetic waves at the receiver antenna. The expressions obtained for the Von Mises distribution can include or not the mutual coupling effect between the elements and are simpler than those obtained for the cosine and the Gaussian distributions of the angle of arrival. The Von Mises distribution produces spatial correlation expressions in terms of Bessel and trigonometric functions. An exact expression for the spatial correlation, taking into account the mutual coupling, for the circular and linear arrays and an arbitrary number of elements are presented. It can be verified, by numerical evaluation of the expressions, that the coupling between the elements correlates the electromagnetic field, and a separation of half wavelength could not be enough to decorrelate them.

1. Introduction

The design of modern communication systems usually requires the statistical characterization of parameters, such as the direction of arrival (DoA) of the electromagnetic wave that reaches the receiver antenna. The knowledge of that parameter is valuable when the target is to limit the effects of interference as well as the gain for undesirable signals [1].

The estimation of DoA has been treated by different authors [1] considering the signal samples captured in the equally spaced elements of antenna arrays. This relevant problem has been addressed in many aspects. A general approach is to consider elements with arbitrary directional characteristics in environments corrupted by noise and interference, characterized by arbitrary covariance matrices.

As an example, in [2], the author addresses the spatial processing of signals with respect to the multiplicity of transmitters and presents the algorithm used in the multiple signal classification (MUSIC) method which gives asymptotically nonbiased estimates of different parameters, such as number of arriving waves, direction of arrival, interference, and noise power. A comparative study of methods based on maximum likelihood (ML) and maximum entropy (ME) is presented. The approach presented in the paper for the classification of multiple signals is general and has wide application. The method may be understood in terms of the geometry of an š‘€-dimensional complex vector space in which the eigenvalues of the covariance matrix of the samples play an essential role.

Another important contribution for spatial signal processing is found in the literature [3]. The authors present an efficient algorithm for ML estimation of the DoA considering multiple emission sources and signals captured by the elements of an antenna array. The estimator can be applied to signals that arrive through multipath propagation. The algorithm is based on an iterative technique referred to as alternating projection (AP), which transforms the nonlinear multivariate maximization problem in a set of unidimensional problems which are easier to simplify. In spite of the convergence achieved for a wide set of simulations, the authors did not assure the convergence for a general problem.

The Estimation of Signal Parameters Via Rotational Invariance Techniques (ESPRIT) algorithm was presented in [4]. Although ESPRIT has been used in a scenario of angle of arrival (AoA) estimation, it can be applied to a wide range of problems, including detection and estimation of parameters of sinusoidal signals in the presence of noise. The technique uses the rotational invariance of signal subspaces, as a consequence of the translational invariance of elements in antenna arrays.

Since 1997, the paper of Godora is considered as a reference in spatial signal processing [1]. The paper presents a detailed and broaden treatment of different schemes to adjust a radiated beam and a variety of adaptive algorithms to process signals in arrays.

In [5] another method for DoA estimation from the samples captured by antenna arrays was presented. The method is based on ESPRIT in conjunction with some algorithms for ML estimation of DoA in array signal processing applications. A new, simple, and computationally efficient approach was introduced. It consists of maximizing the ML function over a set of points (a grid) obtained from the sampled data in the array. The technique, referred to as estimation by data-supported grid search, which has roots in the linear regression statistical literature, presents a performance that is similar to the use of genetic algorithms, with a significantly lower computational cost.

A method for DoA estimation based on the support vector machine (SVM) was presented in [6]. In the paper a multiresolution approach for real-time AoA estimation of multiple signals reaching a planar array was introduced. The method is based on a support vector classifier which uses multiscaling to improve the angular resolution of the signal detection process in the region of incidence of electromagnetic waves. Data obtained from the antenna arrays are iteratively transformed by a customized SVM. As a result, a map of probabilities that a signal arrives at the antenna array from a fixed angular direction is determined.

Besides DoA, another important information in the study of processing techniques of signals captured by antenna arrays is the spatial correlation between the elements. Examples of application of the spatial correlation coefficients and the covariance matrix are presented in [7, 8]. In the first paper, the covariance matrix is used to evaluate the bit error probability of a compact receiver, with maximum ratio combining, under Nakagami fading. In the second paper, the effect of the mutual coupling between randomly located array elements on the performance of an adaptive antenna array (AAA) is investigated.

With the advance of MIMO systems, one can observe a growing need to assess the performance of compact receivers, in which the signal samples at the elements of the array are correlated. In this scenario, it is necessary to characterize the random nature of the directions of arrival using an appropriate probability distribution.

The uniform distribution was widely used to model the DoA. Simplicity is the first reason for its popularity. The second one is the assumption of electromagnetic diffusion isotropy, which can be observed, for instance, in the work of Clarke [9], which assumes uniform distribution for characterizing the DoA of signals that reach the base station, considering multipath. In environments where the electromagnetic diffusion is not isotropic the uniform distribution may not be applied.

That characteristic of the environment changes the autocorrelation function, as well as the power spectrum of the complex envelope of the signal that is captured by the mobile receiver. Alternative distributions, such as raised cosine, Gaussian, and Laplacian, have been proposed in [10ā€“14], and distributions based on geometric models of the channel have also been proposed in [15, 16].

Besides the aforementioned models, the Von Mises distribution has received great attention in the context of spatial signal processing. It was firstly proposed to model the nonisotropic propagation mechanism in [17], and space-time correlation functions were presented. The expressions obtained for the spatial correlation coefficients with Von Mises distribution can be written in terms of Bessel and trigonometric functions, while the correlation coefficients for the Gaussian distribution are written in terms of the complementary error function, with complex parameters [18].

In [19], the authors characterize the nonisotropic DoA using the Von Mises distribution and present functions for the time correlation and power spectral density of the received signals. In [20], this distribution is applied to the computation of the space-time correlation of narrowband multiple-input multiple-output (MIMO) channels subject to Rayleigh fading for a three-dimensional spreading around the mobile station. The authors verified that the nonisotropic diffusion process increases the correlation level as a function of the spacing between the elements of the mobile station antenna.

In [21] the Von Mises distribution is used to determine expressions for the spatial correlation functions of a uniform circular antenna array considering three-dimensional multipath propagation. This distribution is also used in [22] to compute the design parameters of an antenna array in terms of the šœ… adjust parameter.

In this paper, the spatial correlation coefficients of linear and circular antenna arrays are obtained using the Von Mises distribution. The mathematical expressions derived are compared to those obtained using the raised cosine and Gaussian distributions. It is shown that the Von Mises distribution provides expressions that are less complex and leads to similar numerical results when compared to the ones obtained with the raised cosine and Gaussian distributions. To the best of the authorsā€™ knowledge, the mathematical expressions of spatial correlation for an arbitrary š‘„-power cosine distribution for linear array are new. An additional contribution of this paper is the derivation of expressions for the spatial correlation of linear and circular array considering the Von Mises distribution with and without mutual coupling.

2. The Von Mises Distribution

The Von Mises distribution is a particular case of the Von Mises-Fisher probability distribution in a š‘-dimensional sphere in ā„š‘, for š‘=2. The probability density function (pdf), for a unit vector š± of dimension š‘ is given byš‘š‘(š±;šœ‡,šœ…)=š¶š‘(šœ…)š‘’šœ…šš‘‡š±,(1) in which šœ…ā‰„0, ā€–šā€–=1, š‘‡ is the matrix transposition operator, and š¶š‘(šœ…) is a normalization constant:š¶š‘šœ…(šœ…)=š‘/(2āˆ’1)(2šœ‹)š‘/2Iš‘/(2āˆ’1),(šœ…)(2) in which Iš‘£(š‘„) represents the modified Bessel function of the first kind and order š‘£. The parameters š and šœ… represent the average direction and the accumulation of the distribution. An increase in the value of šœ… implies a concentration of mass around the mean š.

The distribution was presented by the German physicist Richard Von Mises, in a paper published in 1918 [23], to model differences between the theoretical and measured atomic weighs. If šœ™ represents the arrival angle of a component that results from the multipath propagation in an urban environment, then the Von Mises distribution is used to model the random variable Ī¦, whose pdf is given byš‘Ī¦(āŽ§āŽŖāŽØāŽŖāŽ©š‘’šœ™)=šœ…cos(šœ™āˆ’šœ™š‘)2šœ‹I0(šœ…),āˆ’šœ‹+šœ™š‘ā‰¤šœ™ā‰¤šœ‹+šœ™š‘,0,otherwise,(3) in which šœ™š‘ represents the average direction of a set of directional components and varies in the interval [0,šœ‹). Plots of š‘Ī¦(šœ™) for several values of šœ… are shown in Figure 1. It can be seen that the Von Mises distribution converges to a normal one š’©(šœ™š‘,1/šœ…) when šœ… increases, that is,limšœ…ā†’āˆžš‘Ī¦(š‘’šœ™)=āˆ’(šœ™āˆ’šœ™š‘)2/2šœŽ2šœŽāˆš2šœ‹,šœŽ2=1šœ….(4)

When šœ… goes to zero, the Von Mises distribution converges to the uniform distribution U(šœ™), that is,limšœ…ā†’0š‘Ī¦(šœ™)=U(šœ™).(5)

The š‘–th moment of the random variable šœ™ is obtained by computing the expected value of š‘’š‘—š‘˜šœ™,š‘šš‘–=12šœ‹I0ī€œ(šœ…)šœ‹+šœ™š‘āˆ’šœ‹+šœ™š‘š‘’š‘—š‘–šœ™š‘’šœ…cos(šœ™āˆ’šœ™š‘)š‘‘šœ™.(6)

The integral (6) is calculated substituting š‘¢(šœ™)=šœ™āˆ’šœ™š‘ and usingš‘’š‘§cos(šœ™)=I0(š‘§)+2āˆžī“š‘™=1Iš‘™(š‘§)cos(š‘™šœ™),(7) which gives the moments of š‘’š‘—š‘–šœ™ for the Von Mises distribution:š‘šš‘–=I1(šœ…)I0(š‘’šœ…)š‘—š‘–šœ™š‘.(8)

Other probability distribution functions used to model the directions of arrival in mobile environments are the cosine and Gaussian distributions, whose pdfs are written respectively asš‘Ī¦āŽ§āŽŖāŽØāŽŖāŽ©š‘˜(šœ™)=š‘šœ‹cosš‘„ī€·šœ™āˆ’šœ™š‘œī€øšœ‹,āˆ’2+šœ™š‘œšœ‹ā‰¤šœ™ā‰¤2+šœ™š‘œ,š‘0,otherwise,Ī¦=š‘˜(šœ™)š‘”ī”2šœ‹šœŽ2šœ™š‘’āˆ’(šœ™āˆ’šœ™š‘œ)2/2šœŽ2šœ™šœ‹,āˆ’2+šœ™š‘œšœ‹ā‰¤šœ™ā‰¤2+šœ™š‘œ,(9) in which the parameters š‘˜š‘ and š‘˜š‘” are used to adjust the pdf areas to a unity value, and š‘„ and šœŽšœ™ control the pdfs shape. The constant š‘˜š‘ is given byš‘˜š‘=īƒ©12š‘„š‘„ī“š‘™=0īƒ©š‘„š‘™īƒŖī‚€šœ‹Sa(2š‘™āˆ’š‘„)2ī‚īƒŖāˆ’1,(10) in which Sa(š‘„)=sin(š‘„)/š‘„ is the sample function.

The pdfs for the Von Mises, Gaussian, and Cosine are shown in Figure 2. Note the similarity of the three functions for a proper choice of the parameters š‘„, šœŽšœ™, and šœ…. This similarity allows the Von Mises distribution to model the DoA in different mobile communications environments.

3. Computation of the Correlation Coefficients

To compute the spatial correlation coefficients, consider that the signal samples received by the elements of an equally spaced š‘-element linear array are given by š±š‘™, for a separation š‘‘. On the other hand, the received samples at the elements of a circular array with radius š‘Ž are given by š±š‘. In vector form the samples are written asš±š‘™=āŽ”āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ£1š‘’āˆ’š‘—š‘˜š‘‘sin(šœ™)ā‹®š‘’āˆ’š‘—(š‘āˆ’1)š‘˜š‘‘sin(šœ™)āŽ¤āŽ„āŽ„āŽ„āŽ„āŽ„āŽ¦š±,(11)š‘=āŽ”āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ£š‘’š‘—š‘˜š‘Žcos(šœ™āˆ’Ģƒšœƒ1)š‘’š‘—š‘˜š‘Žcos(šœ™āˆ’Ģƒšœƒ2)ā‹®š‘’š‘—š‘˜š‘Žcos(šœ™āˆ’Ģƒšœƒš‘)āŽ¤āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ¦,(12) in which the angles Ģƒšœƒš‘› represent the angular position of the elements for the circular array and š‘˜ represents the electromagnetic field wave number 2šœ‹/šœ†. For the uniform circular array, Ģƒšœƒš‘›=2šœ‹(š‘›/š‘).

3.1. Computation of the Coefficients for the Linear Array

The spatial correlation coefficients between the samples received by two elements of a linear array with š‘ dipoles, separated by an equal distance š‘‘, arešœŒī€ŗš‘„(š‘š,š‘›)=šøš‘šš‘„āˆ—š‘›ī€»,(13) in which š‘„āˆ—š‘› is the conjugate of š‘„š‘›.

3.1.1. Correlation Coefficients for a Cosine Distribution

For a cosine distribution, the correlation coefficients are given by the integralšœŒš‘š‘˜(š‘š,š‘›)=š‘šœ‹ī€œšœ‹/2+šœ™š‘œāˆ’šœ‹/2+šœ™š‘œš‘’š‘—(š‘šāˆ’š‘›)š‘˜š‘‘sin(šœ™)cosš‘„ī€·šœ™āˆ’šœ™š‘œī€øš‘‘šœ™.(14) Using Bessel series and writing cosš‘„(šœ™) as a binomial expansion,cosš‘„1(šœ™)=2š‘„š‘„ī“š‘™=0īƒ©š‘„š‘™īƒŖš‘’š‘—(2š‘™āˆ’š‘„)šœ™,(15) one can obtain the real and imaginary parts of šœŒš‘(š‘š,š‘›), respectively, asā„œī€ŗšœŒš‘ī€»=š‘˜(š‘š,š‘›)š‘šœ‹2š‘„š‘„ī“š‘™=0īƒ©š‘„š‘™īƒŖā„›š‘ī€·(š‘šāˆ’š‘›)š‘˜š‘‘,2š‘™āˆ’š‘„,šœ™š‘œī€ø,ā„‘ī€ŗšœŒš‘ī€»=š‘˜(š‘š,š‘›)š‘šœ‹2š‘„š‘„ī“š‘™=0īƒ©š‘„š‘™īƒŖā„š‘ī€·(š‘šāˆ’š‘›)š‘˜š‘‘,2š‘™āˆ’š‘„,šœ™š‘œī€ø,(16) in which the functions ā„›š‘(š‘Ž,š‘,š‘) and ā„š‘(š‘Ž,š‘,š‘) are, respectively, given by (17) presented. Although the integral in (14) can be written in a closed form, a normalization by a constant š‘˜š‘ must be carried out and the constant š‘˜š‘ depends on the value of š‘„:ā„›š‘(š‘Ž,š‘,š‘)=šœ‹J0ī‚€š‘šœ‹(š‘Ž)Sa2ī‚+šœ‹āˆžī“š‘–=1J2š‘–ī‚ƒī‚€šœ‹(š‘Ž)Sa(2š‘–+š‘)2ī‚ī‚€šœ‹+Sa(2š‘–āˆ’š‘)2ī‚ī‚„Ć—cos(2š‘–š‘)+šœ‹āˆžī“š‘–=0J2š‘–+1ī‚ƒī‚€šœ‹(š‘Ž)Sa(2š‘–+1+š‘)2ī‚ī‚€šœ‹āˆ’Sa(2š‘–+1āˆ’š‘)2ā„ī‚ī‚„Ć—cos((2š‘–+1)š‘),š‘(š‘Ž,š‘,š‘)=šœ‹āˆžī“š‘–=1J2š‘–ī‚ƒī‚€šœ‹(š‘Ž)Sa(2š‘–+š‘)2ī‚ī‚€šœ‹āˆ’Sa(2š‘–āˆ’š‘)2ī‚ī‚„Ć—sin(2š‘–š‘)+šœ‹āˆžī“š‘–=0J2š‘–+1(ī‚ƒī‚€(šœ‹š‘Ž)Sa2š‘–+1+š‘)2ī‚ī‚€šœ‹+Sa(2š‘–+1āˆ’š‘)2ī‚ī‚„Ć—sin((2š‘–+1)š‘).(17)

3.1.2. Correlation Coefficients for a Gaussian Distribution

For the Gaussian distribution, the spatial correlation function can be written asšœŒš‘”š‘˜(š‘š,š‘›)=š‘”ī”2šœ‹šœŽ2šœ™ī€œšœ‹/2+šœ™š‘œāˆ’šœ‹/2+šœ™š‘œš‘’š‘—(š‘šāˆ’š‘›)š‘˜š‘‘sinšœ™š‘’āˆ’(šœ™āˆ’šœ™š‘œ)2/2šœŽ2šœ™š‘‘šœ™.(18) The first step in order to solve the integral in (18) is a variable changing. The expansion of the result using Bessel series gives the following expressions for the real and imaginary parts of šœŒš‘”(š‘š,š‘›):ā„œī€ŗšœŒš‘”(ī€»=š‘š,š‘›)2š‘˜š‘”āˆššœ‹āˆžī“š‘™=1J2š‘™((š‘šāˆ’š‘›)š‘˜š‘‘)ā„›š‘”ī€·2š‘™,šœ™š‘œ,šœŽšœ™ī€ø+J0ā„‘ī€ŗšœŒ((š‘šāˆ’š‘›)š‘˜š‘‘),š‘”(ī€»=š‘š,š‘›)2š‘˜š‘”āˆššœ‹āˆžī“š‘™=0J2š‘™+1((š‘šāˆ’š‘›)š‘˜š‘‘)ā„š‘”ī€·2š‘™+1,šœ™š‘œ,šœŽšœ™ī€ø,(19) in whichā„›š‘”ī€œ(š‘Ž,š‘,š‘)=āˆššœ‹/āˆš8š‘āˆ’šœ‹/8š‘ī‚€š‘Žī‚€āˆšcosš‘’2š‘š‘¢+š‘ī‚ī‚āˆ’š‘¢2ā„š‘‘š‘¢,š‘”ī€œ(š‘Ž,š‘,š‘)=āˆššœ‹/8šœŽšœ™š‘āˆšāˆ’šœ‹/8š‘ī‚€š‘Žī‚€āˆšsinš‘’2š‘š‘¢+š‘ī‚ī‚āˆ’š‘¢2š‘‘š‘¢.(20)

Using Eulerā€™s identities, the integrals in (20) and (25) can be written in terms of the function erf(š‘§) as ā„›š‘”āˆš(š‘Ž,š‘,š‘)=šœ‹2[]š‘’cos(š‘Žš‘)š’œ(š‘Ž,š‘)āˆ’sin(š‘Žš‘)ā„¬(š‘Ž,š‘)āˆ’(š‘Žš‘)2/2,ā„(21)š‘”āˆš(š‘Ž,š‘,š‘)=šœ‹2[]sin(š‘Žš‘)š’œ(š‘Ž,š‘)āˆ’cos(š‘Žš‘)ā„¬(š‘Ž,š‘)Ɨš‘’āˆ’(š‘Žš‘)2/2,(22) in whichīƒÆīƒ©šœ‹š’œ(š‘Ž,š‘)=Reerfāˆš8š‘āˆ’š‘—š‘Žš‘āˆš2īƒÆīƒ©āˆ’šœ‹īƒŖīƒ°āˆ’Reerfāˆš8š‘āˆ’š‘—š‘Žš‘āˆš2,ā„¬īƒÆīƒ©šœ‹īƒŖīƒ°(š‘Ž,š‘)=Imerfāˆš8š‘āˆ’š‘—š‘Žš‘āˆš2īƒÆīƒ©āˆ’šœ‹īƒŖīƒ°āˆ’Imerfāˆš8š‘āˆ’š‘—š‘Žš‘āˆš2.īƒŖīƒ°(23)

The function erf(š‘Ž+š‘—š‘) is defined in [24] as the error function for complex argument and can be calculated using the relationserf(š‘„)=1āˆ’š‘’āˆ’š‘„2š‘¤(š‘—š‘„),š‘¤(š‘„)=š‘’āˆ’š‘„2īƒ©1+2š‘—āˆššœ‹ī€œš‘„š‘”=0š‘’āˆ’š‘”2īƒŖ.š‘‘š‘”(24)

3.1.3. Correlation Coefficients for a Von Mises Distribution

Using the Von Mises distribution, the spatial correlation between two samples of the vector š±š‘™ in (11) can be written asšœŒš‘£1(š‘š,š‘›)=2šœ‹I0ī€œ(šœ…)šœ‹+šœ™š‘āˆ’šœ‹+šœ™š‘š‘’š‘—(š‘šāˆ’š‘›)š‘˜š‘‘sinšœ™š‘’šœ…cos(šœ™āˆ’šœ™š‘)š‘‘šœ™.(25)

Using Eulerā€™s identity and the Bessel series expansion for the real and imaginary parts of šœŒš‘£(š‘š,š‘›), it follows thatā„œī€ŗšœŒš‘£(ī€»=2š‘š,š‘›)I0(šœ…)āˆžī“š‘™=1J2š‘™((š‘šāˆ’š‘›)š‘˜š‘‘)š’œš‘™ī€·šœ…,šœ™š‘ī€ø+J0ā„‘ī€ŗšœŒ((š‘šāˆ’š‘›)š‘˜š‘‘),š‘£(ī€»=2š‘š,š‘›)I0(šœ…)āˆžī“š‘™=0J2š‘™+1((š‘šāˆ’š‘›)š‘˜š‘‘)ā„¬š‘™ī€·šœ…,šœ™š‘ī€ø,(26) in which the auxiliary expressions š’œš‘™(š‘Ž,š‘) and ā„¬š‘™(š‘Ž,š‘) are given byš’œš‘™1(š‘Ž,š‘)=ī€œ2šœ‹šœ‹+š‘āˆ’šœ‹+š‘cos(2š‘™šœ™)š‘’š‘Žcos(šœ™āˆ’š‘)š‘‘šœ™=I2š‘™ā„¬(š‘Ž)cos(2š‘™š‘),š‘™(1š‘Ž,š‘)=ī€œ2šœ‹šœ‹+š‘āˆ’šœ‹+š‘sin((2š‘™+1)šœ™)š‘’š‘Žcos(šœ™āˆ’š‘)š‘‘šœ™=I2š‘™+1(š‘Ž)sin((2š‘™+1)š‘).(27)

From (27), the expressions for the real and imaginary parts of the spatial correlation coefficients for an equally spaced array can be written asā„œī€ŗšœŒš‘£(ī€»š‘š,š‘›)=2āˆžī“š‘™=1ī‚µI2š‘™(šœ…)I0ī‚¶J(šœ…)2š‘™ī€·((š‘šāˆ’š‘›)š‘˜š‘‘)cos2š‘™šœ™š‘ī€ø+J0ā„‘ī€ŗšœŒ((š‘šāˆ’š‘›)š‘˜š‘‘),š‘£(ī€»š‘š,š‘›)=2āˆžī“š‘™=0ī‚µI2š‘™+1(šœ…)I0ī‚¶J(šœ…)2š‘™+1ī€·(((š‘šāˆ’š‘›)š‘˜š‘‘)ā‹…sin2š‘™+1)šœ™š‘ī€ø.(28)

3.2. Computation of the Coefficients for the Circular Array

The spatial correlation coefficients for the circular array can be computed from the expected value,šœŒš‘£ī€ŗš‘„(š‘š,š‘›)=šøš‘šš‘„āˆ—š‘›ī€».(29)

3.2.1. Correlation Coefficients for a Cosine Distribution

For a cosine distribution, the correlation coefficients of the circular array are given byšœŒš‘š‘˜(š‘š,š‘›)=š‘šœ‹ī€œšœ‹/2+šœ™š‘œāˆ’šœ‹/2+šœ™š‘œš‘’š‘—š‘˜š‘Žš¶š‘š,š‘›cos(šœ™āˆ’šœ‘š‘š,š‘›)cosš‘„ī€·šœ™āˆ’šœ™š‘œī€øš‘‘šœ™.(30) Writing cosš‘„(šœ™) as shown in (15) and using Bessel series for the complex exponential, one can obtain the real and imaginary parts of šœŒš‘(š‘š,š‘›) asā„œī€ŗšœŒš‘ī€»=š‘˜(š‘š,š‘›)š‘šœ‹2š‘„š‘„ī“š‘™=0īƒ©š‘„š‘™īƒŖā„›š‘ī€·š‘˜š‘Žš¶š‘š,š‘›,2š‘™āˆ’š‘„,šœ™š‘œāˆ’šœ‘š‘š,š‘›ī€ø,ā„‘ī€ŗšœŒš‘ī€»=š‘˜(š‘š,š‘›)š‘šœ‹2š‘„š‘„ī“š‘™=0īƒ©š‘„š‘™īƒŖā„š‘ī€·š‘˜š‘Žš¶š‘š,š‘›,2š‘™āˆ’š‘„,šœ™š‘œāˆ’šœ‘š‘š,š‘›ī€ø,(31) in which the functions ā„›š‘(š‘Ž,š‘,š‘) and ā„›š‘(š‘Ž,š‘,š‘) are given by ā„›š‘(š‘Ž,š‘,š‘)=šœ‹J0ī‚€š‘šœ‹(š‘Ž)Sa2ī‚+šœ‹āˆžī“š‘™=1(āˆ’1)š‘™J2š‘™ī‚ƒī‚€šœ‹(š‘Ž)Sa(2š‘™+š‘)2ī‚ī‚€šœ‹+Sa(2š‘™āˆ’š‘)2ī‚ī‚„Ć—cos(2š‘™š‘)āˆ’šœ‹āˆžī“š‘™=0(āˆ’1)š‘™J2š‘™+1ī‚ƒī‚€šœ‹(š‘Ž)Sa(2š‘™+1+š‘)2ī‚ī‚€šœ‹āˆ’Sa(2š‘™+1āˆ’š‘)2ā„ī‚ī‚„Ć—sin((2š‘™+1)š‘),š‘(š‘Ž,š‘,š‘)=šœ‹āˆžī“š‘™=1(āˆ’1)š‘™J2š‘™ī‚ƒī‚€šœ‹(š‘Ž)Sa(2š‘™+š‘)2ī‚ī‚€šœ‹āˆ’Sa(2š‘™āˆ’š‘)2ī‚ī‚„Ć—sin(2š‘™š‘)+šœ‹āˆžī“š‘™=0J2š‘™+1(ī‚ƒī‚€(šœ‹š‘Ž)Sa2š‘™+1+š‘)2ī‚ī‚€šœ‹+Sa(2š‘™+1āˆ’š‘)2ī‚ī‚„Ć—cos((2š‘–+1)š‘).(32)

3.2.2. Correlation Coefficients for a Gaussian Distribution

For a Gaussian distribution, the correlation coefficients of the circular array are given byšœŒš‘”š‘˜(š‘š,š‘›)=š‘”ī”2šœ‹šœŽ2šœ™ī€œšœ‹/2+šœ™š‘œāˆ’šœ‹/2+šœ™š‘œš‘’š‘—š‘˜š‘Žš¶š‘š,š‘›cos(šœ™āˆ’šœ‘š‘š,š‘›š‘’āˆ’(šœ™āˆ’šœ™š‘œ)2/2šœŽ2šœ™š‘‘šœ™.(33) The real and imaginary parts of šœŒš‘”(š‘š,š‘›) can be calculated using a procedure similar to that used in the linear array. Applying Bessel expansion to complex exponential one can write ā„œ[šœŒš‘”(š‘š,š‘›)] and ā„‘[šœŒš‘”(š‘š,š‘›)] asā„œī€ŗšœŒš‘”(ī€»=š‘š,š‘›)2š‘˜š‘”āˆššœ‹āˆžī“š‘™=1(āˆ’1)š‘™J2š‘™ī€·š‘˜š‘Žš¶š‘š,š‘›ī€øƗā„›š‘”ī€·2š‘™,šœ™š‘œāˆ’šœ‘š‘š,š‘›,šœŽšœ™ī€ø+J0ī€·š‘˜š‘Žš¶š‘š,š‘›ī€ø,ā„‘ī€ŗšœŒš‘”ī€»=(š‘š,š‘›)2š‘˜š‘”āˆššœ‹āˆžī“š‘™=0(āˆ’1)š‘™J2š‘™+1ī€·š‘˜š‘Žš¶š‘š,š‘›ī€øā‹…ā„›š‘”ī€·2š‘™+1,šœ™0āˆ’šœ‘š‘š,š‘›,šœŽšœ™ī€ø,(34) in which ā„›š‘”(š‘Ž,š‘,š‘) is given by (21).

3.2.3. Correlation Coefficients for a Von Mises Distribution

Using the Von Mises distribution for two samples of the vector š‘„š‘ in (12), one obtainsšœŒš‘£ī€œ(š‘š,š‘›)=šœ‹+šœ™š‘āˆ’šœ‹+šœ™š‘š‘’š‘—š‘˜š‘Žš¶š‘š,š‘›cos(šœ™āˆ’šœ‘š‘š,š‘›)2šœ‹I0š‘’(šœ…)šœ…cos(šœ™āˆ’šœ™š‘)š‘‘šœ™,(35) in whichšœ‘š‘š,š‘›=tš‘”āˆ’1ī‚µĢƒšœƒsinš‘šĢƒšœƒāˆ’sinš‘›Ģƒšœƒcosš‘šĢƒšœƒāˆ’cosš‘›ī‚¶,š¶š‘š,š‘›=ī”2ī€·ī€·Ģƒšœƒ1āˆ’cosš‘šāˆ’Ģƒšœƒš‘›.ī€øī€ø(36)

Using Eulerā€™s identity, one can split the integral (35) into two integrals, which correspond to the real and imaginary parts of šœŒš‘£(š‘š,š‘›),ā„œī€ŗšœŒš‘£ī€»=ī€œ(š‘š,š‘›)šœ‹āˆ’šœ‹ī€·cosš‘˜š‘Žš¶š‘š,š‘›ī€·cosš‘¢+šœ™š‘(š‘š,š‘›)ī€øī€ø2šœ‹I0(šœ…)Ɨš‘’šœ…cos(š‘¢)ā„‘ī€ŗšœŒš‘‘šœ™,(37)š‘£ī€»=ī€œ(š‘š,š‘›)šœ‹āˆ’šœ‹ī€·sinš‘˜š‘Žš¶š‘š,š‘›ī€·cosš‘¢+šœ™š‘(š‘š,š‘›)ī€øī€ø2šœ‹I0(šœ…)Ɨš‘’šœ…cos(š‘¢)š‘‘šœ™,(38) in which šœ™š‘(š‘š,š‘›)=šœ™š‘āˆ’šœ‘š‘š,š‘›.

Using the Bessel series for cos(š‘„cosšœ™) and sin(š‘„cosšœ™), the expression for ā„œ[šœŒš‘£(š‘š,š‘›)] can be written asā„œī€ŗšœŒš‘£(ī€»š‘š,š‘›)=2āˆžī“š‘™=1(āˆ’1)š‘™ī‚µI2š‘™(šœ…)I0ī‚¶J(šœ…)2š‘™ī€·š‘˜š‘Žš¶š‘š,š‘›ī€øī€·ā‹…cos2š‘™šœ™š‘ī€ø(š‘š,š‘›)+J0ī€·š‘˜š‘Žš¶š‘š,š‘›ī€ø.(39)

Following a similar procedure for (38), one can find the imaginary part of the correlation coefficients for a circular array with radius š‘Ž and equally spaced elements,ā„‘ī€ŗšœŒš‘£(ī€»š‘š,š‘›)=2āˆžī“š‘™=0(āˆ’1)š‘™ī‚µI2š‘™+1(šœ…)I0ī‚¶J(šœ…)2š‘™+1ī€·š‘˜š‘Žš¶š‘š,š‘›ī€øī€·(ā‹…cos2š‘™+1)šœ™š‘(ī€ø.š‘š,š‘›)(40)

As one can observe from (16), (19), (28), (39), and (40), the spatial correlation coefficients obtained for the Von Mises distribution are simpler and computationally more appropriate than the expressions obtained for the cosine and Gaussian distributions. The expressions for the correlation coefficients for the Von Mises distribution are written only in terms of Bessel functions weighted by trigonometric functions, while the coefficients obtained for the Gaussian distributions are written in terms of Bessel functions weighted by complex error functions. The coefficients expressions for the cosine distribution are obtained using two double summations of Bessel functions weighted by sums of sample functions and trigonometric functions.

4. Effect of the Mutual Coupling on the Correlation Coefficients

A radio wave induces an electric current in the element array when it reaches the element. This induced current radiates an electromagnetic field that affects other elements around them. Thus, the received signal in a particular element of the array reflects not only the intensity of the desired signal but also the intensity of signals generated by adjacent elements or other conductive object close to the antenna. This effect, known as mutual coupling, changes the phase distribution of the electric current in the array elements. As a result, gain, bandwidth, radiation pattern, and input impedance of an antenna array are affected [25, 26].

The mutual coupling is affected by the separation and the current distribution of the array elements by the wavelength and by the objects located in the near field region. Generally, the most central element of linear and planar arrays are more affected by the coupling [27]. This nonuniform behavior requires individual techniques of impedance matching for each element.

The direction of arrival of the incident wave also affects the coupling. Generally, the direction of arrival and coupling are highly correlated. This occurs more often in arrays that present many phase adjustments. In this case, there is an unbalance among the power of the elements of the array and a consequent changing in coupling between the elements [28].

When the mutual coupling is considered, the dipole length must be taken into account. In this case, the radiated field expressions must be computed for the near field region. The current intensity in each element contributes to the radiated beam, as well as to the distortion of the current distributions in the neighbor elements [29].

To calculate the linear array spatial correlation coefficients, subject to the coupling effect, it is necessary to establish the relation between the voltage vector š•, obtained at the array dipoles, and the signal sample vector š’, without coupling [30]. This relation is [7]š•=š™āˆ’1š’,(41) in which š™ and š’ are given byāŽ”āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ£š‘š™=1+11š‘šæš‘12š‘šæš‘13š‘šæā‹Æš‘1š‘€š‘šæš‘21š‘šæš‘1+22š‘šæš‘23š‘šæā‹Æš‘2š‘€š‘šæš‘ā‹®ā‹®ā‹®ā‹±ā‹®š‘€1Zšæš‘š‘€2š‘šæš‘š‘€3š‘šæš‘ā‹Æ1+š‘€š‘€š‘šæāŽ¤āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ¦,(42)āŽ”āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ£š‘’š’=š‘—0š‘˜š‘‘sinšœ™š‘’š‘—1š‘˜š‘‘sinšœ™ā‹®š‘’š‘—(š‘€āˆ’1)š‘˜š‘‘sinšœ™āŽ¤āŽ„āŽ„āŽ„āŽ„āŽ„āŽ¦.(43) It is important to point out that the definition of the mutual impedance matrix in (42) is accurate only for transmitting antennas. For receiving antenna arrays, such as the ones considered for DoA application in this paper, the mutual coupling effect characterized by the matrix in (42) is not accurate because the mutual impedance elements are calculated based on the current distributions of transmitting antenna elements with excitations being at the antenna ports. A more accurate modeling of the antenna mutual impedances, the so-called ā€œreceiving mutual impedanceā€, can be found in [31ā€“33]

However, (42) can be used if the receiving antenna arrays for DoA application are excited by electromagnetic waves coming from a short distance (e.g., indoor transmissions), then the current distribution will be different for each of the antenna element.

In the matrix š‘€Ć—š‘€ in (42), the elements š‘mš‘› represent the self-impedance of the š‘šth dipole when š‘š=š‘› and the mutual impedance between the š‘šth dipole and the š‘›-dipole when š‘šā‰ š‘›. Considering that the impedance matrix š™āˆ’1 (inverse of š™) is given byš™āˆ’1=āŽ”āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ£š‘Ž11š‘Ž12ā‹Æš‘Ž1š‘€š‘Ž21š‘Ž22ā‹Æš‘Ž2š‘€š‘Žā‹®ā‹®ā‹±ā‹®š‘€1š‘Žš‘€2ā‹Æš‘Žš‘€š‘€āŽ¤āŽ„āŽ„āŽ„āŽ„āŽ„āŽ¦,(44) the voltage vector isāŽ”āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ£š•=š‘€ī“š‘–=1š‘Ž1š‘–š‘’š‘€š‘—(š‘–āˆ’1)š‘˜š‘‘sinšœ™ī“š‘–=1š‘Ž2š‘–š‘’š‘—(š‘–āˆ’1)š‘˜š‘‘sinšœ™ā‹®š‘€ī“š‘–=1š‘Žš‘€š‘–š‘’š‘—(š‘–āˆ’1)š‘˜š‘‘sinšœ™āŽ¤āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ¦.(45)

If one takes two samples š‘Ÿš‘š and š‘Ÿš‘› of the voltage vector š•, the square of the correlation coefficient modulus can be written as||šœŒš‘šš‘›||2=1š‘ƒš‘šš‘ƒš‘›ī€œš‘Ÿš‘šš‘Ÿāˆ—š‘›š‘(šœ™)š‘‘šœ™,(46) in which š‘ƒš‘š represents the average power of a component from the received signal at the š‘šth antenna array element. For an antenna with š‘€ elements, it is given byš‘ƒš‘š=ī€œ||š‘Ÿš‘š||2š‘(šœ™)š‘‘šœ™,š‘š=1,2,ā€¦,š‘€.(47)

Substituting one of the vector samples š• into (47), it follows thatš‘ƒš‘š=ī€œšœ‹+šœ™š‘āˆ’šœ‹+šœ™š‘|||||š‘€ī“š‘›=1š‘Žš‘šš‘›š‘’š‘—(š‘›āˆ’1)š‘˜š‘‘sinšœ™|||||2=ī€œš‘(šœ™)š‘‘šœ™šœ‹+šœ™š‘āˆ’šœ‹+šœ™š‘š‘€ī“š‘€š‘–=1ī“š‘™=1š‘Žš‘šš‘–š‘Žāˆ—š‘šš‘™š‘’š‘—(š‘–āˆ’š‘™)š‘˜š‘‘sinšœ™š‘(šœ™)š‘‘šœ™,(48) in which š‘š=1,2,ā€¦,š‘€.

Applying the Von Mises distribution in (48), it follows thatš‘ƒš‘š=š‘€ī“š‘€š‘–=1š‘–>š‘™ī“š‘™=1š‘Žš‘šš‘–š‘Žāˆ—š‘šš‘™ā„((š‘–āˆ’š‘™)š‘˜š‘‘,šœ™š‘+,šœ…)š‘€ī“š‘–=1š‘–<š‘™š‘€ī“š‘™=1š‘Žš‘šš‘–š‘Žāˆ—š‘šš‘™ā„ī€·(š‘–āˆ’š‘™)š‘˜š‘‘,šœ™š‘ī€ø+,šœ…š‘€ī“š‘–=1||š‘Žš‘šš‘–||2,(49) in whichā„ī€·(š‘–āˆ’š‘™)š‘˜š‘‘,šœ™š‘ī€ø=ī€œ,šœ…šœ‹+šœ™š‘āˆ’šœ‹+šœ™š‘š‘’š‘—(š‘–āˆ’š‘™)š‘˜š‘‘sinšœ™š‘’šœ…cos(šœ™āˆ’šœ™š‘)2šœ‹I0(šœ…)š‘‘šœ™=š‘š‘–š‘™+š‘—š›½š‘–š‘™,(50) withš‘š‘–š‘™=2āˆžī“š‘›=1ī‚µI2š‘›(šœ…)I0ī‚¶J(šœ…)2š‘›ī€·((š‘–āˆ’š‘™)š‘˜š‘‘)cos2š‘›šœ™š‘ī€ø+J0š›½((š‘–āˆ’š‘™)š‘˜š‘‘),š‘–š‘™=2āˆžī“š‘›=0ī‚µI2š‘›+1(šœ…)I0ī‚¶J(šœ…)2š‘›+1ī€·((š‘–āˆ’š‘™)š‘˜š‘‘)sin(2š‘›+1)šœ™š‘ī€ø.(51)

Substituting the result from (50) into (49),š‘ƒš‘š=āŽ›āŽœāŽœāŽœāŽš‘€ī“š‘€š‘–=1ī“š‘™=1š‘™<š‘–š‘Žš‘šš‘–š‘Žāˆ—š‘šš‘™š‘š‘–š‘™+š‘€ī“š‘€š‘–=1ī“š‘™=1š‘™>š‘–š‘Žš‘šš‘–š‘Žāˆ—š‘šš‘™š‘š‘–š‘™āŽžāŽŸāŽŸāŽŸāŽ āŽ›āŽœāŽœāŽœāŽ+š‘—š‘€ī“š‘€š‘–=1ī“š‘™=1š‘™<š‘–š‘Žš‘šš‘–š‘Žāˆ—š‘šš‘™š›½š‘–š‘™āˆ’š‘€ī“š‘€š‘–=1ī“š‘™=1š‘™>š‘–š‘Žš‘šš‘–š‘Žāˆ—š‘šš‘™š›½š‘–š‘™āŽžāŽŸāŽŸāŽŸāŽ +š‘€ī“š‘–=1||š‘Žš‘šš‘–||2.(52)

From (52) one observes that when š‘–<š‘™ the terms š‘Žš‘šš‘–š‘Žāˆ—š‘šš‘™ and š‘Žāˆ—š‘šš‘–š‘Žš‘šš‘™ are complex conjugates. Therefore,š‘ƒš‘š=2š‘€ī“š‘€š‘–=1ī“ā„œī€½š‘Žš‘™=1š‘™>š‘–š‘šš‘–š‘Žāˆ—š‘šš‘™ī€¾š‘š‘–š‘™+š‘€ī“š‘–=1||š‘Žš‘šš‘–||2+2š‘€ī“š‘€š‘–=1ī“š‘™=1š‘™>š‘–ā„‘ī€½š‘Žš‘šš‘–š‘Žāˆ—š‘šš‘™ī€¾š›½š‘–š‘™.(53)

A similar expression can be obtained for the power š‘ƒš‘›. Using (46), the integral āˆ«š‘Ÿš‘šš‘Ÿāˆ—š‘›š‘(šœ™)š‘‘šœ™ can be calculated asī€œš‘Ÿš‘–(šœ™)š‘Ÿāˆ—š‘™=(šœ™)š‘(šœ™)š‘‘šœ™š‘€ī“š‘€š‘›=1ī“š‘š=1š‘Žš‘–š‘›š‘Žāˆ—š‘™š‘šī€·š‘š‘›š‘š+š‘—š›½š‘›š‘šī€ø,(54) in which š‘š‘›š‘š+š‘—š›½š‘›š‘š can be computed using (51). Therefore, the spatial correlation coefficients are calculated as||šœŒš‘›š‘š||2=1š‘ƒš‘›š‘ƒš‘š|||||š‘€ī“š‘€š‘–=1ī“š‘™=1š‘Žš‘›iš‘Žāˆ—š‘šš‘™ī€·š‘š‘–š‘™+š‘—š›½š‘–š‘™ī€ø|||||2.(55)

For the case of linear dipole elements of length š‘™, with š‘™=š‘›šœ†/2, š‘›=1,3,5,ā€¦, aligned side by side and centrally fed, the real and imaginary parts of the mutual impedance between two dipoles, referred to as Dipole 1 and Dipole 2, can be obtained using the Electromagnetic Field (EMF) method and can be written as [34]š‘…12=šœ‚0ī€ŗī€·š‘¢4šœ‹2Ci0ī€øī€·š‘¢āˆ’Ci1ī€øī€·š‘¢āˆ’Ci2,š‘‹ī€øī€»12šœ‚=āˆ’0ī€ŗī€·š‘¢4šœ‹2Si0ī€øī€·š‘¢āˆ’Si1ī€øī€·š‘¢āˆ’Si2,ī€øī€»(56) in whichš‘¢0š‘¢=š‘˜š‘‘,1ī‚€āˆš=š‘˜š‘‘2+š‘™2ī‚,š‘¢+š‘™2ī‚€āˆš=š‘˜š‘‘2+š‘™2ī‚.āˆ’š‘™(57) For those equations, š‘˜=2šœ‹/šœ† is the wave number, šœ‚0 is the medium impedance, approximately 120šœ‹ ohms, and Ci(š‘„) and Si(š‘„) are the integral sine and cosine functions. Therefore, the impedance between two dipoles š‘š and š‘› is given by š‘š‘šš‘›=š‘…š‘šš‘›+š‘—š‘‹š‘šš‘›, in whichš‘…š‘šš‘›=šœ‚0ī‚øī€·4šœ‹2Ciš‘˜š‘‘š‘šš‘›ī€øī‚µš‘˜ī‚µī”āˆ’Ciš‘‘2š‘šš‘›+š‘™2ī‚µš‘˜ī‚µī”+š‘™ī‚¶ī‚¶āˆ’Ciš‘‘2š‘šš‘›+š‘™2,š‘‹āˆ’š‘™ī‚¶ī‚¶ī‚¹š‘šš‘›šœ‚=āˆ’0ī‚øī€·4šœ‹2Sš‘–š‘˜š‘‘š‘šš‘›ī€øī‚µš‘˜ī‚µī”āˆ’Siš‘‘2š‘šš‘›+š‘™2ī‚µš‘˜ī‚µī”+š‘™ī‚¶ī‚¶āˆ’Siš‘‘2š‘šš‘›+š‘™2,āˆ’š‘™ī‚¶ī‚¶ī‚¹(58) withš‘‘š‘šš‘›=āŽ§āŽŖāŽØāŽŖāŽ©š‘Žī”š‘‘|š‘šāˆ’š‘›|,forthelineararray,2ī€·ī€·Ģƒšœƒ1āˆ’cosš‘šāˆ’Ģƒšœƒš‘›ī€øī€ø,forthecirculararray.(59)

The equation for the computation of the distance between the circular array elements was obtained from the Euclidean distance between two elements located at points Ģƒšœƒ(š‘Žcosš‘šĢƒšœƒ,š‘Žsinm) and Ģƒšœƒ(š‘Žcosš‘›Ģƒšœƒ,š‘Žsinš‘›).

5. Numerical Evaluation of the Results

For the numerical evaluation of the expressions presented in this paper, half wavelength linear dipoles were considered with central feeding. For those dipoles, the mutual impedance vectors between the first element, taken as a reference, and the remaining elements are given by (58), and (59). Therefore, the mutual impedances vectors for a linear and a circular array with six elements are given, respectively, byš™š‘™=āŽ”āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ£āŽ¤āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ¦,š™1.505667034+š‘—0.86272872360.047354099āˆ’š‘—0.3785965596āˆ’0.062961878+š‘—0.20416918290.052751548āˆ’š‘—0.1363497266āˆ’0.043681351+š‘—0.10171054900.036932473āˆ’š‘—0.0808845309š‘=āŽ”āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ¢āŽ£āŽ¤āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ„āŽ¦.1.505667034+š‘—0.86272872360.047415842āˆ’š‘—0.3811347251āˆ’0.219332270+š‘—0.1091267749āˆ’0.063208579+š‘—0.2058290449āˆ’0.219332270+š‘—0.10912677490.047415842āˆ’š‘—0.3811347251(60)

Both vectors are normalized by the complex conjugate of the dipole self-impedance. The mutual impedance matrices have the form given in (42) and can be obtained from the elements of the vectors š™š‘™ and š™š‘.

Figures 3 and 4 show plots of the spatial correlation between elements 1 and 3 of the linear array, using the Von Mises distribution to model the AoA. For those curves, šœ™š‘=30āˆ˜ and šœ™š‘=60āˆ˜ represent the average AoA for the signal components.

Note that in Figure 3(a) and Figure 4(a) the elements 1 and 3 are more correlated for an angle šœ™š‘=60āˆ˜ than for an angle šœ™š‘=30āˆ˜. This shows the dependence between the correlation and the electromagnetic wave direction of arrival. Furthermore, for the same angle of arrival, there is a dependence between the spatial correlation and the parameter šœ….

Considering Figures 3(b) and 4(b), one can note that increasing values of šœ… corresponds to a highly concentrated beam of electromagnetic waves that arrive at the array and control the degree of correlation. This beam can be produced in anisotropic propagation environments where the reflected components of the electromagnetic waves are added in the direction of the antenna array. This concentration of the beam increases the amplitude of the induced current in some elements of the array and radiate with more intensity to the neighbor elements. Hence, the effect of coupling is increased. This behavior can also be seen in Figure 5(b) for the circular array. The circular distribution of the elements contributes to increasing the correlation because the elements that receive the radiated beam have a direct view of all other elements. In linear arrays the central elements do not have a direct view of the end elements.

Figures 5(a) and 5(b) show different plots of the spatial correlation, for a circular array, as a function of š‘Ž/šœ†, for a six element array. The curves were obtained for different values of šœ… and šœ™š‘=60āˆ˜.

From Figure 5(b) one can note that the spatial correlation between elements 1 and 3 can be zero at š‘Ž/šœ†ā‰ˆ1/2, even for šœ… equals 4 or 8. Note that when šœ…>4 the Von Mises probability density function can approximate a Gaussian distribution, which is commonly used to model AoA in mobile environments.

For the linear and circular configurations the mutual coupling effect increases the correlation between the samples at the parallel elements. As expected, the coupling is affected by the distance between the dipoles, by the angle of arrival, and by the Von Mises distribution parameter šœ…. For šœ…=8 the curves present higher correlation values for š‘‘=šœ†/2.

The amount and shape of the obstacles around the array also determine the mutual coupling between the elements [35]. When the obstacles are concentrated in a specific point of the spatial region nearby the antenna, electromagnetic waves reflected in this agglomerate of obstacles can be concentrated around a main direction and the beam that reaches the array can become more collimated, depending on the variance of the direction of arrival around the mean direction. A collimated beam of waves reaching the array leads to an increase in the power captured by the elements. As a result, the intensity of the induced currents will be augmented, and the effect of coupling will increase. The parameter that determines how well the Von Mises pdf approximates the Gaussian pdf is šœ…. A limiting behavior of the distribution is that it approximates the Gaussian pdf with variance šœŽ2=1/šœ…. Hence, a high šœ… leads to a small variance for the Gaussian approximation and the beam of waves that reaches the array collimates and the intensity of the distribution of induced currents in the elements increases.

6. Conclusions

This paper presented a mathematical comparison between the spatial correlation expressions for cosine, Gaussian, and Von Mises probability distributions, for linear and circular antenna arrays. The expressions obtained for the Von Mises distribution can include or not the mutual coupling effect between the elements and are simpler than those obtained for the cosine and the Gaussian distributions of the angle of arrival. The use of the Von Mises distribution allows the spatial correlation expressions to depend only on Bessel and trigonometric functions. An exact expression for the spatial correlation is also presented, considering the mutual coupling, for the linear and circular arrays and an arbitrary number of half wave dipole elements. From the numerical evaluation of the expressions, it is observed that in some cases the separation of šœ†/2 is not sufficient to decorrelate the signal.


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Copyright © 2011 Wamberto J. L. Queiroz et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

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