Interference-Based Decode and Forward Scheme Using Relay Nodes in Heterogeneous Networks

Abstract

This paper proposes interference-based decode and forward scheme that utilizes relay stations (RSs). In Long-Term-Evolution (LTE-) Advanced, heterogeneous networks in which femto- and picocells are overlaid onto macrocells are extensively discussed. However, interference between macro- and pico(femto)cells arises due to their different transmit power levels. Unlike conventional cooperative transmission schemes, the RS decodes interference in the first transmit timing period and forwards it to the user equipment (UE) in the second period. Moreover, cooperative transmission can be achieved without stopping the transmission from the base station (BS) to UE when forwarding the interference from the RS to the UE by utilizing the fact that signal-to-noise power ratio (SNR) between the RS and UE is much greater than that between the BS and UE. The basic performance of the proposed method is shown based on computer simulation. Moreover, the interference temperature and shadowing effect are measured when considering the coexistence between macro- and femtocells, and the performance of the proposed method is verified using measured shadowing effect.

1. Introduction

Due to the immense popularity of mobile phones and wireless LAN systems, increasing the data rate within a limited spectrum is one of the most important goals for wireless system design. Macrocells, the service areas which are one to several kilometers, were introduced in conventional cellular systems. On the other hand, femto- and picocells are currently the focus because small cells can enhance the frequency utilization and can be established using a low-power-consuming base station (BS) that requires a small installation space. In Long-Term-Evolution (LTE-) Advanced, heterogeneous networks are extensively discussed in addition to traditional well-planned macrocell deployment to further improve the frequency utilization [1–3]. In heterogeneous network deployment, low power nodes such as femto-, pico-, and relay nodes are placed throughout a macrocell layout, and they are placed generally in an unplanned manner. Hence, interference between macro- and pico(femto)cells occurs because the transmission power of pico(femto)cells is different from that of macrocell and the service coverage areas are different between these cells.

In this paper, we consider a macrocell system consisting of a BS and user terminals (UEs) and propose an interference-based decode and forward technique using a relay station (RS) to cancel the interference from pico- or femtocell. In recent years, cooperative transmission using RSs has been primarily used to improve the overall system capacity or to obtain a diversity gain [4, 5]. On the other hand, RSs can also be utilized for interference cancellation [6, 7]. The RS forwards information regarding the interference that is used by a receiver to decode the desired signal. Ideas on forwarding interference were considered in [6, 7] for the case when a destination node receives the desired signal and interference with small power, and instead of forwarding the desired signal, the RS forwards information regarding the interference. Moreover, interference cancellation techniques with the aid of the RS for cognitive radio are proposed [8, 9]. However, the treatment in [6–9] is information-theoretic and did not explain the concrete procedure of how to use the RS in detail. In this work, we focus on a more practical setting with concrete system/modulation parameters, as well as a complete procedure for channel estimation, which is a prerequisite for actualizing distributed interference cancellation.

Interference-based decode and forward scheme using an RS for cognitive radio was proposed in [10]. In this method, the RS decodes and forwards the interference to a UE in a secondary system from a BS in the primary system using periodic training signals in the primary system. However, the time for interference transfer from the RS to UE is overhead in this method. We proposed a method that addresses this problem by utilizing the fact that the signal-to-noise ratio (SNR) between the RS and BS is greater than that between the BS and UE [11]. The optimal position of the relay stations by the proposed method is clarified based on computer simulation [11]. This paper brings significantly broadened treatment of the proposed method. (i)The basic performance of the proposed method is evaluated in more detail. In particular, the proposed method is effective compared to the conventional adaptive array, regardless of the condition of SIR, SNRs of BS/RS and RS/UE. (ii)Not only zero forcing (ZF) but also minimum mean square error (MMSE) algorithms with 2-element adaptive array at the UE are evaluated as the reference schemes, because MMSE algorithm is evaluated for the interference rejection between multicells for LTE-Advanced [12]. (iii)The performance of the proposed method is evaluated using measured data regarding a shadowing effect when considering coexistence between marco and femtocells.

When considering the RS as a virtual antenna which helps the UE from the interference, the configuration using the proposed method can be regarded as one of configurations regarding distributed antenna system.

The rest of the paper is organized as follows. Section 2 describes the target scenario and defines the problem to be addressed. Section 3 presents the proposed technique for interference cancellation using an RS. Section 4 provides quantitative performance analysis of the proposed scheme with theoretical propagation models. The affect on shadowing with the measured data is evaluated in Section 5. Section 6 concludes the paper.

2. Target Scenario and Problem Definition

Figure 1 shows a configuration for heterogeneous networks in LTE-Advanced [1]. In such heterogeneous networks, picocells, femtocells, and relays are deployed inside the service area of a macrocell in order to enhance the frequency utilization and guarantee the quality of service in high traffic areas. The picocell service area is several tens of meters. Femtocells have drawn much attention recently because their transmission power level is very low and thus they only require a low-power-consuming BS and small installation space. We focus on the coexistence between macro- and pico(femto)cells that use the same frequency band. However, the interference between macro- and pico(femto)cell occurs because the transmission power of pico(femto)cells is different from that of macrocells and the service coverage areas are different between macro- and pico(femto)cells. In this paper, we focus on the interference from a pico(femto) BS (P(F)-BS) to a set of macro-user equipment (M-UE), and we propose interference-based decode and forward scheme using RSs.

Figure 1 

Configuration of heterogeneous network.

Figure 2 shows the signal format of the BS in macro- and pico(femto)cells. Frequency division duplex (FDD) is generally used in macrocell BS (M-BS). On the other hand, pico- or femto-BS (P-BS or F-BS) employing time division duplex (TDD) is assumed in this paper. Both FDD and TDD are included as the standard of LTE-Advanced [13]. In such a scenario, P-BS transmits a signal using time slot 1 and receives a signal using time slot 2 as in Figure 2. In this paper, we utilize this feature in the proposed method.

Figure 2 

Signal format of base station in macro- and pico(femto)cells.

3. Proposed Method

The proposed method cancels the interference at the M-UE from the P-BS by using the aid of as RS in the macrocell (M-RS). Let us assume a downlink scenario. The RS with decode and forward generally receives the desired signal from the BS in time slot 1 and this signal is forwarded to the UE via the RS in the next time slot (time slot 2) [4, 5]. Figure 3 shows the concept of the proposed method. Although three macrocells are considered as general system configuration in Figure 1, for the sake of ease, a macrocell is considered in Figure 3. In the proposed method, the M-RS decodes the interference from the P-BS (F-BS) at time slot 1 and the decoded interference is forwarded to the M-UE during time slot 2 when the interference from the P-BS (F-BS) arrives at the M-UE. We assume that M-BS has multiple antennas but each RS has only one antenna in this paper. For simplification, P-BS is treated as the interference hereafter but F-BS is also treated as interference in this paper. The transmit timing of the preamble signals for CSI estimation is shown in Figure 4. The proposed scheme can be explained in the following six steps. (1)All CSI (M-BS/M-UE, M-BS/M-RE, M-RS/M-UE, P-BS/M-UE, and P-BS/M-RS) estimations are carried out using the preamble in Figure 4. (2)The M-BS controls the transmit weight in order not to arrive the signal at the M-RS by using the CSI in Step 1 during the data period of time slot 1. (3)The interference incurred during the data period of time slot 1 is decoded using the received signal at the M-RS and the CSI from Step 1. (4)The M-RS transmits the interference obtained in Step 3 to the M-UE during the next period of time slot 2. (5)The interference incurred during the data period for time slot 2 is estimated from the received signal at the M-UE and the CSI from Step 1. (6)The desired signals, 𝑆₁(𝑡) and 𝑆₂(𝑡), for the M-UE are estimated using the interference decoded in Step 5, the received signal in Steps 2 and 4, and the CSI from Step 1.

Figure 3 

Concept of proposed method.

Figure 4 

Transmit timing of preamble signals for CSI estimation.

Steps 1 to 3 are employed during time slot 1 and Steps 4 to 6 are employed during time slot 2. In Step 1, we divide the period for the training sequence into three parts as shown in Figure 4 in order to estimate all the required CSIs. During Period 1, the M-BS and M-RS stop their transmissions to the M-UE such that only the CSI of the interference from the P-BS to M-UE and M-RS is acquired. The received signals, 𝑋_𝑃1,𝑈(𝑡) and 𝑋_𝑃1,𝑅(𝑡), at the M-UE and M-RS during Period 1 (1≤𝑡≤𝑇_𝑝1,𝑇_𝑝1=𝑇_𝑝/3 in Figure 4) are given below: 𝑋_𝑃1,𝑈(𝑡)=ℎ_𝑃𝑈𝐼_𝑃1(𝑡)+𝑁_𝑈(𝑡),𝑋_𝑃1,𝑅(𝑡)=ℎ_𝑃𝑅𝐼_𝑃1(𝑡)+𝑁_𝑅(𝑡), (1)(2) where ℎ_𝑃𝑈 and ℎ_𝑃𝑅 denote the channel responses of the interfering signals for M-UE and M-RS, respectively. 𝑇_𝑝 denotes the length of the preamble signal for P-BS. 𝐼_𝑃1(𝑡) represents the known preamble signals from the P-BS in Period 1. 𝑁_𝑈(𝑡) and 𝑁_𝑅(𝑡) represent the thermal noise for the M-UE and M-RS from the P-BS, respectively.

During Periods 2 and 3, signals are transmitted by the M-BS and M-RS, respectively. The M-BS (M-RS) stops its transmission in Period 2 (3). The received signals, 𝑋_𝑃2,𝑈(𝑡) and 𝑋_𝑃3,𝑈(𝑡), at the M-UE for Period 2 (𝑇_𝑝1+1≤𝑡≤𝑇_𝑝2,𝑇_𝑝2=2𝑇_𝑝1) and Period 3 (𝑇_𝑝2+1≤𝑡≤𝑇_𝑝) are given as 𝑋_𝑃2,𝑈(𝑡)=ℎ_𝐵𝑈𝑆_𝑃(𝑡)+ℎ_𝑃𝑈𝐼_𝑃2(𝑡)+𝑁_𝑈(𝑡),𝑋_𝑃3,𝑈(𝑡)=ℎ_𝑅𝑈𝑆_𝑃(𝑡)+ℎ_𝑃𝑈𝐼_𝑃3(𝑡)+𝑁_𝑈(𝑡), (3)(4) where ℎ_𝐵𝑈 and ℎ_𝑃𝑈 denote the channel responses from the M-BS and M-RS to the M-UE, respectively. 𝐼_𝑃2(𝑡) and 𝐼_𝑃3(𝑡) represent the known preamble signals from P-BS in Periods 2 and 3, respectively. 𝑆_𝑃(𝑡) denotes the known preamble signals from the M-BS and M-RS in Periods 2 and 3, respectively. During Period 2, M-RS receives the signal form M-BS and interference from P-BS. The received signals, 𝑋_𝑃2,𝑅(𝑡), at the M-RS for Period 2 are given as 𝑋_𝑃2,𝑅(𝑡)=ℎ_𝐵𝑅𝑆_𝑃(𝑡)+ℎ_𝑃𝑅𝐼_𝑃2(𝑡)+𝑁_𝑅(𝑡), (5) where ℎ_𝐵𝑅 denotes the channel response from the M-BS to M-RS.

All CSIs are obtained using (1) to (5). The least square (LS) criteria is adopted for CSI estimation. The estimated CSIs of P-BS/M-UE and P-BS/M-RS are obtained using (1) and (2), respectively, as given below: ℎ_𝑃𝑈=1𝑇_𝑝1^𝑇𝑝1_𝑡=1𝑋_𝑃1,𝑈(𝑡)𝐼_𝑃1(𝑡),ℎ_𝑃𝑅=1𝑇_𝑝1^𝑇𝑝1_𝑡=1𝑋_𝑃1,𝑅(𝑡)𝐼_𝑃1(𝑡). (6)(7)

The estimated CSIs of M-BS/M-UE, M-BS/M-RS and M-RS/M-UE are obtained by using (3) and (7), respectively, as follows: ℎ_𝐵𝑈=1𝑇_𝑝1^𝑇𝑝2_{𝑡=𝑇𝑝1+1}𝑋_𝑃2,𝑈(𝑡)−ℎ_𝑃𝑈𝐼_𝑃2(𝑡)𝑆_𝑃(𝑡),ℎ_𝐵𝑅=1𝑇_𝑝1^𝑇𝑝2_{𝑡=𝑇𝑝1+1}𝑋_𝑃2,𝑅(𝑡)−ℎ_𝑃𝑅𝐼_𝑃2(𝑡)𝑆_𝑃(𝑡),ℎ_𝑅𝑈=1𝑇_𝑝1^𝑇𝑝3_{𝑡=𝑇𝑝2+1}𝑋_𝑃3,𝑈(𝑡)−ℎ_𝑃𝑈𝐼_𝑃3(𝑡)𝑆_𝑃(𝑡). (8)(9)(10) As shown in (6) to (10), 𝑇_𝑝1 is required as the number of symbols for the channel estimation. Throughout the evaluation, 𝑇_𝑝1 is set to be five.

The propagation channel between M-BS and M-RS is not basically changed because these stations do not move, unlike M-UE. Hence, we can consider that the propagation channel is not changed between Steps 1 and 2. When considering the channel between M-BS and M-UE, the adaptive weight may be changed due to the Doppler shift. On the other hand, transmission speed for one time slot can be assumed to be much shorter than the Doppler frequency when considering recent broadband wireless communication. However, when the Doppler frequency is very high, the adaptive weight might be changed. We must consider this issue as one of future works.

In the second step (Step 2), the M-BS transmits a signal to the M-UE with an antenna pattern that creates a null toward the M-RS during the data period for time slot 1 in Figure 3. The received signals at the M-UE and M-RS are expressed as 𝑋_𝑡1,𝑈(𝑡)=ℎ_𝐵𝑈𝑆₁(𝑡)+ℎ_𝑃𝑈𝐼(𝑡)+𝑁_𝑈(𝑡),𝑋_𝑡1,𝑅(𝑡)=ℎ_𝑃𝑅𝐼(𝑡)+𝑁_𝑅(𝑡), (11)(12) where 𝑆₁(𝑡) and 𝐼(𝑡) represent unknown data signals for the M-UE from the M-BS and P-BS, respectively. Hence, the M-UE must decode and cancel interference 𝐼(𝑡) without any information pertaining to the interference.

𝑆₁(𝑡) cannot be decoded using the procedure in Steps 1 and 2. On the other hand, interference 𝐼(𝑡) can be estimated at the M-RS using (12) and ℎ_𝑃𝑅 obtained in Step 1. In Step 3, the M-RS decodes the interference that occurs during the data period of time slot 1. The decoded interference, 𝐼(̃𝑡), at the M-RS is obtained using (7) and (12) as 𝐼̃(𝑡)=𝑋_𝑡1,𝑅(𝑡)ℎ_𝑃𝑅=ℎ_𝑃𝑅ℎ_𝑃𝑅𝐼(𝑡)+𝑁_𝑅(𝑡)ℎ_𝑃𝑅(𝑡)+𝑁≈𝐼^𝑅(𝑡)ℎ_𝑃𝑅. (13) Here, interference-to-noise power ratio (INR) at the M-RS is 𝐸[|ℎ_𝑃𝑅|²/|𝑁_𝑅(𝑡)|²]. When the INR is large, the second term on the right side of (13) is negligible. In Step 4, the M-RS transmits interference 𝐼(̃𝑡) estimated in Step 3 to the M-UE using the next data period for time slot 2 in Figure 3. The M-BS transmits a signal to the M-UE using this period. The received signal at the M-UE is denoted by 𝑋_𝑡2,𝑈(𝑡)=ℎ_𝐵𝑈𝑆₂(𝑡)+ℎ_𝑅𝑈𝐼̃(𝑡)+𝑁_𝑈(𝑡), (14) where 𝑆₂(𝑡) represents unknown data signals for the M-UE from the M-BS at time slot 2.

In Step 5, after the transmission of the interference, the interference from the P-BS during the data period for time slot 1, 𝐼(̃𝑡), is estimated by using the received signal in (14). First, (14) is changed using (10) as: 𝑋_𝑡2,𝑈(𝑡)ℎ_𝑅𝑈=ℎ_𝐵𝑈ℎ_𝑅𝑈𝑆₂(𝑡)+ℎ_𝑅𝑈ℎ_𝑅𝑈𝐼̃(𝑡)+𝑁_𝑈(𝑡)ℎ_𝑅𝑈. (15) When ℎ_𝑅𝑈≈ℎ_𝑅𝑈, signal-to-interference power ratio (SIR) and INR at M-UE are denoted as 𝐸[|ℎ_𝐵𝑈|²/|ℎ_𝑅𝑈|²] and 𝐸[|ℎ_𝑅𝑈|²/|𝑁_𝑈(𝑡)|²], respectively. It is reasonable to assume that 𝐸[|ℎ_𝑅𝑈|²] is much larger than 𝐸[|ℎ_𝐵𝑈|²] and 𝐸[|𝑁_𝑈(𝑡)|²], because the M-RS should be located near the M-UE. In other word, the SIR is very small and the INR is very large. Hence, the first and third terms on the right side of (15) can be approximately assumed to be much smaller than the second term on the right side of (15). Note that SNR, 𝐸[|ℎ_𝐵𝑈|²/|𝑁_𝑈(𝑡)|²] is not small and the first term on the right side of (15) is not zero. As a result, when we ignore the first and third terms on the right side of (15), (15) can be approximated as 𝑋_𝑡2,𝑈(𝑡)ℎ_𝑅𝑈≈𝐼̃(𝑡)≡𝐼̂(𝑡). (16)

In Step 6, the desired signals, 𝑆₁(𝑡) and 𝑆₂(𝑡), can be estimated using interference 𝐼(̂𝑡) estimated in Step 5, received signals 𝑋_𝑡1,𝑈(𝑡) and 𝑋_𝑡2,𝑈(𝑡) in Steps 2 and 4, and CSIs ℎ_𝐵𝑈, ℎ_𝑃𝑈, and ℎ_𝑅𝑈 obtained in Step 1. The estimated desired signals, 𝑆₁(𝑡) and 𝑆₂(𝑡), can be denoted as. 𝑆₁(𝑡)=𝑋_𝑡1,𝑈(𝑡)−ℎ_𝑃𝑈𝐼̂(𝑡)ℎ_𝐵𝑈,𝑆₂(𝑡)=𝑋_𝑡2,𝑈(𝑡)−ℎ_𝑅𝑈𝐼̂(𝑡)ℎ_𝐵𝑈. (17)

4. Basic Characteristics of the Proposed Method

In this section, we evaluate the performance of the proposed method by computer simulation. Figure 5 represents the configurations of the proposed and reference scheme. We compare the proposed interference cancellation method (Method (A)) to a reference scheme (Method (B)), an adaptive array using ZF/MMSE. For a fair comparison, the total number of antennas at the transmitter and receiver sites are identical for Methods (A) and (B). The numbers of antennas at the M-BS and the M-UE are two, respectively, in Method (B). The number of antennas at the M-BS is two and that at the M-RS plus M-UE is also two in Method (A). In Method (B), the M-UE uses an adaptive array with ZF/MMSE [12]. When using the ZF algorithm, the decoded signal is denoted as 𝑆(𝑡)𝐼̃(𝑡)=ℎ_𝑆1ℎ_𝐼1ℎ_𝑆2ℎ_𝐼2⁻¹𝑋_𝑈1𝑋_𝑈2=𝐡_𝑆𝐡_𝐼⁻¹𝐗_𝑈=𝐇⁻¹𝐗_𝑈, (18) where 𝐡_𝑆=[ℎ_𝑆1,ℎ_𝑆2]^𝑇 and 𝐡_𝐼=[ℎ_𝐼1,ℎ_𝐼2]^𝑇 denote the channel responses for the M-UE from the M-BS and P-BS, respectively. 𝐗_𝑈=[𝑋_𝑈1,𝑋_𝑈2]^𝑇 is the received signal vector at the M-UE. When using the MMSE algorithm, the decoded signal is denoted as 𝑆(𝑡)𝐼̃(𝑡)=𝐇^𝐻𝐇+𝜎²𝐔⁻¹𝐇^𝐻𝐗_𝑈, (19) where 𝐔is 2 × 2 identity matrix and 𝜎² is the noise power. A total transmit power by M-BS and M-RS in the proposed method is the same with that by M-BS in the conventional method.

(a) Configuration for Method (A) Method (A): Proposed method

(b) Configuration for Method (B) Method (B): Adaptive array using ZF/MMSE algorithms

Figure 5 

Proposed and reference schemes.

Transmissions from the M-BS to M-UE in the macrocell use adaptive modulation. Table 1 gives the required SNRs for different modulation levels. The SNR for each modulation scheme is given in Table 1 for the bit error rate (BER) of 5×10⁻³ [14]. For all the methods, the modulation level is decided based on the instantaneous SNR. The modulation scheme for the interference is QPSK.

Table 1 

Required SNR for different modulation levels.

The total transmission rate, 𝑅, is defined as ∑𝑅=^{𝑁𝐹𝑘=1}𝑅(𝑘)𝑁_𝐹,𝑅(𝑘)=𝑀_𝑎[1−BER(𝑘)], (20) where 𝑁_𝐹 represents the number of frames. 𝑀_𝑎 denotes the number of bits per symbol when applying the adaptive modulation. 𝑅(𝑘) and BER(𝑘) are the transmission rate and BER for the 𝑘th frame, respectively. In the simulation, we set the length per frame to 600 and 𝑁_𝐹=20000. A Rayleigh fading environment is assumed among all nodes. In the evaluation, we did not consider channel codes in order to evaluate the basic ability of the proposed method.

First, the transmission rate is evaluated versus the SIR in Figure 6, in order to confirm the effectiveness of the approximation in (16). Here, we assume that the desired signal (𝑆) and the interference (𝐼) are the signals from the M-BS and M-RS to the M-UE at time slot 2 in Figure 3, respectively. For comparison, the results when only the desired signal is decoded are shown. Figure 6 shows that the transmission rate is improved when the SIR is decreased. When the SIR is less than –10 dB, the degradation compared to the transmission rate with the upper bound is less than 1 bit/s. Hence, the approximation in (16) is effective when considering the SNR between the M-RS and M-UE to be greater than that between the M-BS and M-UE.

Figure 6 

Transmission rate versus SIR.

The SNR between the M-RS and M-UE is a very important parameter that determines the ability for decoding the interference. The transmission rates of the proposed method versus the SNR between the M-RS and M-UE are plotted in Figure 7. The average SNR between the M-BS and M-UE and the SIR between the M-BS and P-BS for the M-UE are set to 20 and 0 dB, respectively. The average transmission rate for time slots 1 and 2 is shown in Figure 7. As shown in Figure 7, the transmission rates for time slots 1 and 2 are improved according to the SNR between the M-RS and M-UE and both transmission rates are almost the same. Moreover, the proposed method obtains a higher transmission rate than that for 2-element adaptive array using ZF/MMSE algorithm when the SNR between the M-RS and M-UE is greater than 28 dB. Note that the average bit rate by the MMSE algorithm is almost same with that by the ZF algorithm. The proposed method is effective compared to the adaptive array with ZF/MMSE when the SNR between the M-RS and M-UE is 8 dB higher than that between the M-BS and M-UE.

Figure 7 

Transmission rate versus SNR between M-RS and M-UE.

Figure 8 plots the transmission rates of the proposed method and ZF/MMSE adaptive array (Method (B)) versus the SNR between the M-BS and M-UE. Note that the average bit rate by the MMSE algorithm is almost the same with that by the ZF algorithm except very small SNR. The results are plotted when the SNR between the M-RS and M-UE is 10/15 dB (𝛼 in Figure 8), greater than that between the M-BS and M-UE. As shown in the figure, by applying the proposed method, the transmission rate is improved compared to that for Method (B), when the SNR between the B-RS and M-UE is greater than 10 and 7 dB, respectively, and when 𝛼 is 10 and 15 dB.

Figure 8 

Transmission rate versus SNR between M-RS and M-UE.

5. Performance Evaluation Considering Coexistence between Macro- and Femtocells Using Measured Shadowing Effect

In this section, the performance of the proposed method is evaluated when considering the coexistence between macro and femtocells using measured shadowing effect. Since there are UEs that do not belong to a closed subscriber group (CSG) BS in a femtocell, such UEs might give/receive interference to/from the femtocell [1]. Moreover, the femtocell is generally used in indoor scenarios, and the propagation characteristics between the femto- and macrocells are different from those inside a macrocell. We performed measurements to obtain the shadowing characteristics between femto- and macrocells and inside a macrocell and reflected the results in a computer simulation.

Figure 9 shows the considered measurement environment. The measurements are taken in the Faculty of Engineering building of Niigata University in Japan. The M-UE is located in a parking area and moved around Courses 1 to 10 in Figure 9. The M-BS and F-BS are located at the top of the building and the 4th floor in Figure 9, respectively. The antenna heights of the M-BS and F-BS are 22.5 and 16.5 m, respectively. The height of the M-UE is 1 m. The F-BS is located in the place in Figure 10, because the influence of the shadowing might be changed by the difference of the place in Figure 10. The radio frequency is 2.2 GHz and a continuous wave (10 W) is transmitted from the M-BS or F-BS to the M-UE. The received power and shadowing effect are measured. The shadowing effect is obtained by calculating the standard deviation of median values in the received power. The median values are obtained with the distance of 1 m. We assume the scenario where the interference from the femtocell arrives at the M-UE when the M-BS communicates with the M-UE.

Figure 9 

Measurement environment.

Figure 10 

Location of femto-BS.

Figure 11 denotes the received power for the desired signal (M-BS/M-UE, outdoor) and interference (F-BS/M-UE, Cases 1, 2, and 3) when considering Courses 1 to 10. Table 2 show the standard deviation of the shadowing effect for the M-BS/M-UE and F-BS/M-UE, respectively. As shown in Figure 11, the power of desired signal is 3 dB higher than that of interference (Case 1) when considering CDF = 50%. Due to the influence of penetration loss in indoor, the received powers by Case 2 and 3 are lower than that by Case 1. Table 2 shows that the standard deviation of the shadowing is for the desired signal 5.1 and from 4.8 to 6.6 for the interference, respectively. Since outdoor-to-indoor propagation is considered when considering the interference from/to the femtocell to/from the M-UE, the range of the standard deviation for the F-BS/M-UE is larger than that for the M-BS/M-UE.

Table 2 

Standard deviation of shadowing.

Figure 11 

Received powers for desired signal and interference. Outdoor: desired signal, interference: Cases 1 to 3.

The transmission bit rate is evaluated using the measured standard deviation of the shadowing. Table 3 gives the simulation parameters. Considering the value on the standard deviation of shadowing, the results of outdoor and Case 2 in Table 2 are used for M-BS/M-UE and F-BS/M-UE transmissions, respectively. Figure 12 denotes the locations of M-BS, M-UE, F-BS, and M-RS. Three femtocells are assumed to be located inside a macrocell. F-BSs are randomly located inside the service area in M-BS. M-UE is also located inside the service area in M-BS. We employed the simulation where the location on F-BSs and M-UE is changed. The trial number is 10000. Regarding the basic parameter in Table 3, we refer to the parameters which are used in [2]. Regarding the cell radius of M-BS, when the cell radius is 289 m [2], we assume the cell size of 8 times, because the effectiveness of the relay station should be evaluated.

Table 3 

Simulation parameters.

Figure 12 

Location of M-BS, M-UE, F-BS, and M-RS.

Since the evaluation using heterogeneous path loss conditions is essential when considering heterogeneous networks [15, 16], the propagation pathloss model proposed in [17] is used in this paper. Model C2, which is used for typical macrocell non-line-of-sight (NLOS) scenarios, is adopted for the path loss between the M-BS and M-UE. Since we consider the interference from the F-BS to M-UE, Model B1, which is used for microcell line-of-sight (LOS) scenarios, is adopted for the path loss between the P-BS and M-UE. Model B1 is also used for the pathloss between the M-RS and M-UE. The path loss between the M-BS and M-RS is Model B5f (NLOS), which is used for relay transmission between the M-BS and M-RS. The relay stations are located at the position of 𝑑/2 in Figure 12. Four relay stations are assumed in Figure 12. When considering the propagation of M-BS/M-RS, M-RS/M-UE, and F-BS/M-RS, the values on the standard deviation of shadowing are used in those in [17]. The number of relays, 𝑁_𝑅, is changed from 4 to 16 in a circular arrangement. The other simulation conditions are the same as those described in Section 4. We assume that the M-UE and M-RS can exchange the information with a certain interval, and that the M-UE can ideally select M-RS from which SNR to M-UE is the highest. We evaluate average transmission rate which means average cell throughput of M-BS. In the evaluation, we did not consider channel codes in order to evaluate the basic ability of the proposed method.

In the simulation, we assume that the M-RS obtains the information regarding the adaptive modulation scheme by using the control channel of F-BS, because the M-RS can receive only interference by the F-BS. Moreover, we assume that the M-RS correctly informs the information regarding adaptive modulation scheme by the F-BS to the M-UE.

Figure 13 shows the relationship between the transmission rate versus the number of relays, 𝑁_𝑅. Not only QPSK modulation but also adaptive modulation for F-BS is assumed in Figure 13. The figure shows that the transmission rate is improved when 𝑁_𝑅 is increased, but the performance becomes gradually saturated when 𝑁_𝑅≥6 when considering only QPSK modulation for F-BS. Although the transmission rate is degraded compared to the case with only QPSK modulation for F-BS when assuming adaptive modulation for F-BS, we confirm that the transmission rate is gradually increased by the aid of increasing number of relays. The reason why the average bit rate (of M-UE) decreases when F-BS is allowed to use adaptive modulation is that the performance by the proposed method depends on the interference decoding in (13) at the M-RS. When the higher modulation scheme in F-BS is employed, the higher interference-to-noise power Ratio (INR) is required at the M-RS for the interference decoding. Moreover, it is shown that the proposed method outperforms the ZF/MMSE schemes even when 𝑁_𝑅=4. The average bit rate by the MMSE algorithm is almost the same with that by the ZF algorithm.

Figure 13 

Transmission rate versus transmit power of F-BS when considering shadowing effect.

6. Conclusion

This paper proposed interference-based decode and forward method using the RSs in heterogeneous networks. The RS in a macrocell system decodes and forwards the interference from the pico(femto)cell to the UE, and the UE can decode the signal without stopping the signal reception from the BS by utilizing the higher SNR between the RS and UE compared to that between BS and UE in the proposed method. We clarified the effectiveness of the proposed method compared to using the conventional adaptive array with ZF and MMSE algorithms when the SNR between the RS and UE is 8 dB greater than that between the BS and UE. Moreover, we confirmed the effectiveness of the proposed method based on evaluation using the measured data for shadowing effects when considering the coexistence between macro- and femtocells.

As for the future work, we evaluate the influence when changing the service area of macrocell/picocell, because the interference power is largely affected by the service area of macrocell/picocell. In this paper, our aim was to propose the basic technique when the relay nodes can be applied and we focused on the basic ability of the interference cancellation by using the proposed method. On the other hand, hybrid ARQ is adopted as one of the important techniques in LTE-Advanced and the evaluation by using the proposed method including the channel codes is essential for the future work.