International Journal of Antennas and Propagation

International Journal of Antennas and Propagation / 2014 / Article

Research Article | Open Access

Volume 2014 |Article ID 479189 |

L. A. Haralambiev, H. D. Hristov, "Radiation Characteristics of 3D Resonant Cavity Antenna with Grid-Oscillator Integrated Inside", International Journal of Antennas and Propagation, vol. 2014, Article ID 479189, 6 pages, 2014.

Radiation Characteristics of 3D Resonant Cavity Antenna with Grid-Oscillator Integrated Inside

Academic Editor: Ahmad Safaai-Jazi
Received17 Jul 2013
Accepted01 Dec 2013
Published16 Jan 2014


A three-dimensional (3D) rectangular cavity antenna with an aperture size of 80 mm 80 mm and a length of 16 mm, integrated with a four-MESFET transistor grid-oscillator, is designed and studied experimentally. It is found that the use of 3D antenna resonant cavity in case of small or medium gain microwave active cavity antenna leads to effective and stable power combining and radiation. The lack of lateral cavity diffraction and radiation helps in producing a directive gain of about 17 dB and radiation aperture efficiency bigger than 75% at a resonance frequency of 8.62 GHz. Good DC to RF oscillator efficiency of 26%, effective isotropic radiated power (EIRP) of 5.2 W, and SSB spectral power density of −82 dBc/Hz are found from the measured data. The 3D antenna cavity serves also as a strong metal container for the solid-state oscillator circuitry.

1. Introduction

The miniaturization in antennas is of great significance for the modern mobile and portable aircraft and spacecraft wireless electronic systems. However, in addition to the structural, technological, power, and other limitation factors valid for all electronic devices, the miniaturization in antennas is inherently restricted by the space electromagnetic radiation mechanism.

Great antenna size reduction is achieved by using the resonant field phenomenon. The resonant antenna is usually commensurable in size with the design wavelength. If the outer resonant antenna surface is excited in resonance, the antenna is termed exoresonant. Examples of such antennas are the resonant dipoles or monopoles, loops, and slots. By analogy, if some antenna comprises a cavity tuned in resonance it is named endoresonant or simply cavity antenna (CA).

Depending on the configuration and inside field mode structure the passive single-cavity antennas are divided into two basic classes: closed or 3D cavity antennas [15] and open or beam-waveguide (Fabry-Perot) cavity antennas [613]. The classic optical or quasi-optical Fabry-Perot resonator is a laterally open, one-dimensional (1D) resonant cavity with a big transverse dimension and length , where is the resonance cavity design frequency and is an integer number. Frequently in practice, the microwave Fabry-Perot or 1D cavity antennas do not obey the above quasi-optical size condition. The above referenced 1D cavity antennas are based on fundamental-mode cavity resonators with a smaller transverse size of about several wavelengths and a length near to half the wavelength. As a rule, this compromise is on account of the antenna radiation properties. Most of the 1D passive cavity antennas have relatively low aperture radiation efficiency. For example, the radiation efficiency is 15–53% in [8], 41% in [9], 43% in [10], and 30–40% in [11]. An exception is claimed in [7], where a maximum efficiency of 75% is predicted.

Both 3D and 1D cavity antennas have partially reflecting surfaces (PRS) named also electromagnetic band gap (EBG) structures that serve as antenna radiation apertures. An arrangement of a 3D passage cavity and 3D or 1D radiating cavity forms a double-cavity antenna [3].

Due to the cavity-field resonance the passive 3D and 1D antennas are narrowband, with a typical frequency bandwidth from about 1 to 3% and a gain of 15–20 dB. For these bandwidth and gain ranges the cavity antennas are much smaller in length, volume, and weight compared to the equal in aperture nonresonant antennas.

Along with the development of compact high-power communication, radar, and radionavigation equipment the need of a large-scale integration of electronic devices like microwave/mm-wave detectors, amplifiers, oscillators, phase-shifters, and so forth with the antenna structures is taking place, and thus, the antennas become active devices. The active antennas belong to the so-called functionally small antennas, a term that applies where additional performance is being added without increasing the antenna size [14].

An efficient power combining in a free space or in a cavity antenna volume is possible using a distributed (array) oscillator approach. The oscillating solid-state devices (Gunn or IMPATT diodes, MESFET or HEMT transistors, etc.) are mounted in a grid array. The grid-oscillator arrays act simultaneously as power combiners and antennas.

The open cavity antenna-oscillator (CAO) approach for combining the output powers of multiple microwave devices has been first studied by Mink in [15]. There, a large relative to the design wavelength Fabry-Perot cavity of two reflectors, plane total reflector and perforated (PRS) radiation shell, with a spherical curvature is applied. Such a large relative to wavelength 1D cavity is more suitable for millimeter and submillimeter (quasi-optical) antenna-oscillators. In [15], the planar array of IMPATT or Gunn-diodes is placed in a small distance from the total plane reflector.

Intensive and fruitful work on efficient 1D cavity power combining devices is described later on in [1619]. However, because of the bigger diffraction loss and inner cavity field distribution change, their radiation characteristics are inferior compared to those of the corresponding passive cavity antennas.

For small and medium aperture-size microwave and long-mm-wave passive and active antennas the use of 3D antenna cavities has some advantages.(i)There is no diffraction loss as in the case of the laterally open quasi-optical cavities, and thus better radiation characteristics and higher gain and efficiency are possible.(ii)The metal closed cavity is a robust container for the solid-state electronic circuitry placed inside.

Early work on the power combining in 3D round cavity antenna-oscillators is found in [20]. These are X-band single-cavity and double-cavity antenna-oscillators containing Gunn-diodes integrated in half-loop feeds, where power combining efficiency is bigger than 80% and aperture radiation efficiency is 40–50% for the two-cavity and bigger than 60% for the single-cavity antenna oscillators.

In this paper an effective 3D cavity antenna-oscillator comprising an array of MESFET oscillator elements and radiating through a rectangular slotted-array aperture is contrasted to a similar in shape and dimensions 3D passive cavity antenna.

2. Profiles and Resonant Features of Passive and Active Cavity Antennas

2.1. Profiles of Passive Cavity Antennas

Profile cross-sections of 3D and 1D passive cavity antennas are sketched in Figures 1(a) and 1(b), respectively. Each antenna cavity is fed in the middle of the back reflector wall (BW) by a flanged (F) hollow waveguide (WG) through an end-wall iris (I). The 3D cavity antenna (3D CA) is laterally closed by a side wall (SW), while the 1D cavity antenna (1D CA) is laterally open. A3 and A1 are the transverse profile cavity dimensions, while L3 and L1 are the lengths of 3D cavity and 1D cavity, correspondingly. Both cavity antennas, 3D CA and 1D CA, have partially reflecting aperture wall (AW).

2.2. Profiles of Active Cavity Antennas-Oscillators

Figures 2(a) and 2(b) illustrate the profiles of 3D and 1D cavity antennas-oscillators.

The passive cavity antennas illustrated above (Figure 1) are converted here into the active (antennas-oscillators) sketched in Figure 2. It is supposed that these antennas-oscillators have the same cavity shapes and dimensions as the corresponding passive ones but are fed by inner (integrated) autonomous grid-MESFET oscillators (GOs).

2.3. Mode Spectrum Density in Lossless Cavities

In the 3D or closed cavity a number of natural field modes can be excited. Their resonant frequencies form a discrete spectrum in the cavity volume with a spectrum density given by the asymptotic Rayleigh-Jeans formula [21] where is the number of field modes for a unit frequency increment and is the free-space light velocity. Obviously, the mode discrete spectrum density becomes bigger with the volume and frequency increase ().

In the 1D or Fabry-Perot cavity the spectral density does not depend on the frequency but on the cavity length only Or, evidently, the resonant frequencies form an equidistant (constant-density) spectrum.

It is concluded that as a result of the lateral opening in the 1D cavity there are no transverse field reflections and transverse cavity modes. Thus, the latter are selectively radiated and only the axial standing-wave modes are left inside. This is the physical explanation for the frequency spectrum thinning effect.

Like the cavity resonator the passive or active cavity antenna is supposed to operate in a single-mode regime; that is, in a specific frequency band only a single characteristic mode exists. Most often this is the fundamental mode with the lowest resonant frequency, which is achieved by choosing a proper cavity size and field excitation and suppression (filtering) of unwanted modes.

3. Passive and Active 3D Cavity Antenna Designs

3.1. Passive Cavity Antenna Design

The passive cavity antenna (Figure 1(a)) comprises a 3D rectangular cavity. The antenna is designed for a resonant frequency of 9.0 GHz (or resonant wavelength of 33.33 mm). The cavity is excited by means of -mode rectangular waveguide through an end-wall capacitive iris 23 mm 4 mm in size.

Our experience with the passive cavity antennas has shown that the fundamental cavity field mode very much prevails over the nearest higher-order TE and TH modes if the characteristic transverse cavity size is less than , where is the cavity -mode resonance frequency [24]. The cavity aperture wall (AW) is chosen square in shape with dimensions as follows: aperture side (or ) and cavity length (or ).

For a lossless and nonradiating rectangular cavity the resonance frequency of the fundamental mode is easily found by The corresponding cavity wavelength is

This passive cavity antenna radiates through a slotted (partially reflecting) aperture printed on a copper-clad dielectric substrate of thickness 1.5 mm and permittivity and loss tangent equal to 2.3 and 0.005, respectively. The aperture slot array consists of equal slots, with a size of each.

3.2. Cavity Antenna-Oscillator Design

The passive cavity antenna described in Section 3.1 is converted here into the cavity antenna-oscillator sketched in Figure 3. This active antenna has the cavity of the passive one but is fed by an inner grid of MESFET transistor oscillators, similar to those described in [22, 23]. Each MESFET-oscillator element has the configuration, dimensions, and electric data shown in Figure 3(a). The grid plate is centered on the cavity wall opposite to the slotted aperture wall (Figure 3(b)). A feedback coupling occurs between the basic cavity field mode and the oscillator array dipole elements. This phenomenon leads to an injection phase-locking and high efficient power combing in the closed cavity volume. Like the semitransparent slotted aperture plate, the MESFET grid oscillator circuit is printed on a copper-clad Teflon substrate. The detuning effect of RF induced biasing caused by the cavity field mode to the MESFET oscillator action is not considered initially. The grid-oscillator is designed for an action in free space. As expected, after its insertion in the antenna high-Q resonant cavity, the oscillator phase noise and stability performance have been improved. Small adjustments of the carrier frequency and radiation efficiency have been done with a change of the cavity and dipoles’ lengths.

The MITSUBISHI MGF 1303B MESFETs are employed in the grid oscillator. Within the X-band each transistor provides about 16 mW CW power.

3.3. Experimental Results for Passive and Active Cavity Antennas

Figure 4 illustrates the copolarization (solid lines) and cross-polarization (dashed lines) radiation patterns of the studied cavity antenna-oscillator measured at 8.62 GHz in the main antenna planes: E-plane (right curves) and H-plane (left curves). Evidently, the copolarization E-plane radiation pattern has narrower beamwidth and lower maximum sidelobes, while the maximum H-plane cross-polarization is smaller compared to the E-plane one.

The frequency spectrum of cavity antenna-oscillator measured in antenna far-field region is shown in Figure 5. The carrier oscillator frequency is 8.62 GHz and the measured SSB spectral power density is −82 dBc/Hz at 100 KHz off the carrier frequency. Overall DC to RF efficiency of 26% and effective isotropic radiated power (EIRP) of 5.2 W are computed from the experimental data. Further increase of DC to RF efficiency and EIRP is possible by further diminishing of mutual coupling in the grid-dipole array and material loss in the oscillator circuitry and antenna cavity.

In Table 1 the measured radiation characteristics of the passive cavity antenna at the resonance frequency of 8.779 GHz and active cavity antenna-oscillator at the carrier oscillator resonance frequency are contrasted. These are beamwidth BW and first sidelobe level SLL of the E-plane and H-plane radiation patterns, fundamental resonance frequency in GHz, antenna directive gain in dB, radiation aperture efficiency , in %, where is the antenna aperture surface, DC to RF efficiency in %, EIRP in W, and SSB spectral density in dBc/Hz.

Antenna parametersPassive antennaActive antenna

(1) H-plane rad. pattern
  BW, deg2425
  SLL, dB−21−18
(2) E-plane rad. pattern
  BW, deg2223
  SLL, dB−23−22
(3) , GHz8.779 8.623
(4) G, dB17.3 16.9
(5) , %78.4 74.8
(6) DC to RF efficiency, %26.0
(7) EIRP, W5.2
(8) SSB, dBc/Hz−82.0

As it is chosen in the design text above, both passive and active cavity antennas have the same structures and dimensions and differ only in their field sources: narrow capacitive iris (I) fed by a rectangular waveguide in the case of passive antenna and grid-oscillator (GO) integrated within the cavity on its back cavity wall RW.

From Figures 4 and 5 and Table 1 several important comments follow.(1)The basic radiation parameters (BW, SLL, , etc.) of the cavity antenna-oscillator reasonably deteriorate compared to those of the original passive cavity antenna. These effects are due to the inevitable field distribution change because of the presence of the grid-oscillator circuitry.(2)The antenna-oscillator directive gain and efficiency compared to those of the passive cavity antenna are falling down by only 0.4 dB and 3.6%, respectively.(3)Both passive and active 3D cavity antennas enjoy high aperture gain efficiency of about 75–80%. In contrast, the 1D cavity antennas for the same relatively small cavity and aperture dimensions typically have about 1.5–2.0 times smaller radiation efficiency.(4)Insertion of grid-oscillator circuitry printed on a dielectric substrate diminishes the cavity resonance frequency, from 8.779 GHz to 8.623 GHz, but it could be corrected simply by changing slightly the cavity length and optimizing the mutual coupling between the oscillator-array dipole elements.

4. Conclusions

An undersized 3D cavity antenna integrated with a four-MESFET-transistor grid-oscillator power combiner is designed and studied experimentally. Very good DC to RF oscillator efficiency of 26% and effective isotropic radiated power (EIRP) of 5.2 W are obtained from the measured data. It is proved that the use of 3D antenna resonant cavity instead of 1D parallel-plane one in case of small and medium aperture-size and gain microwave passive and active antennas has an effective power combining action. The lack of diffraction loss due to the lateral cavity opening leads to a higher directive gain of about 17 dB and radiation aperture efficiency bigger than 75%. In addition, the 3D cavity serves as a strong metal container for the solid-state oscillator circuitry inside.

Conflict of Interests

The authors declare that there is no conflict of interests regarding the publication of this paper.


The authors acknowledge the Chilean Science Agency CONICYT for the support within the Anillos Project ACT-53 and Fondecyt Project 1120714.


  1. S. Jacobsen, E. Andersen, and M. Gronlund, “An antenna illuminated by a cavity resonator,” Proceedings of the IEEE, vol. 11, pp. 1431–1435, 1963. View at: Google Scholar
  2. A. M. Jassim and H. D. Hristov, “Cavity feed technique for slot-coupled microstrip patch array antenna,” IEE Proceedings: Microwaves, Antennas and Propagation, vol. 142, no. 6, pp. 452–456, 1995. View at: Publisher Site | Google Scholar
  3. A. Kumar and H. D. Hristov, Microwave Cavity Antennas, Artech House, Norwood, Mass, USA, 1989.
  4. S. V. Savov and H. D. Hristov, “Cavity-backed slot array analysis,” IEE Proceedings H, vol. 134, no. 3, pp. 280–284, 1987. View at: Google Scholar
  5. F. J. Paoloni, “A cavity-backed resonant slot array—theory and measurement,” IEEE Transactions on Antennas and Propagation, vol. 28, no. 2, pp. 259–263, 1980. View at: Google Scholar
  6. G. V. Trentini, “Partially reflecting sheet arrays,” IRE Transactions on Antennas and Propagation, pp. 666–670, 1956. View at: Google Scholar
  7. A. Foroozesh and L. Shafai, “On the design of high-gain resonant cavity antennas using different highly-reflective frequency selective surfaces as the superstrates,” in Proceedings of the IEEE International Symposium on Antennas and Propagation and CNC-USNC/URSI Radio Science Meeting (AP-S/URSI '10), July 2010. View at: Publisher Site | Google Scholar
  8. A. P. Feresidis and J. C. Vardaxoglou, “High gain planar antenna using optimised partially reflective surfaces,” IEE Proceedings: Microwaves, Antennas and Propagation, vol. 148, no. 6, pp. 345–350, 2001. View at: Publisher Site | Google Scholar
  9. R. Sauleau, P. Coquet, T. Matsui, and J.-P. Daniel, “A new concept of focusing antennas using plane-parallel Fabry-Perot cavities with nonuniform mirrors,” IEEE Transactions on Antennas and Propagation, vol. 51, no. 11, pp. 3171–3175, 2003. View at: Publisher Site | Google Scholar
  10. N. Guérin, S. Enoch, G. Tayeb, P. Sabouroux, P. Vincent, and H. Legay, “A metallic Fabry-Perot directive antenna,” IEEE Transactions on Antennas and Propagation, vol. 54, no. 1, pp. 220–223, 2006. View at: Publisher Site | Google Scholar
  11. Y. Ge, K. P. Esselle, and T. S. Bird, “A method to design dual-band, high-directivity ebg resonator antennas using single-resonant, single-layer partially reflective surfaces,” Progress in Electromagnetics Research C, vol. 13, pp. 245–257, 2010. View at: Publisher Site | Google Scholar
  12. P. J. Klass, “Helicopter stabilized by microwave beam,” Aviation Week and Space Technology, vol. 22, pp. 85–89, 1968. View at: Google Scholar
  13. J. R. Brauer, “Rectangular beam waveguide resonator and antenna,” IEEE Transactions on Antennas and Propagation, vol. 20, no. 5, pp. 595–601, 1972. View at: Google Scholar
  14. K. Fujimoto, A. Henderson, K. Hirasava, and J. James, Small Antennas, Research Studies Press, 1987.
  15. J. W. Mink, “Quasi-optical power combining of solid-state millimeter-wave sources,” IEEE Transactions on Microwave Theory and Techniques, vol. 34, no. 2, pp. 273–279, 1986. View at: Google Scholar
  16. Z. B. Popovic, R. M. Weikle, M. Kim, and D. B. Rutledge, “A 100-MESFET planar grid oscillator,” IEEE Transactions on Microwave Theory and Techniques, vol. 39, no. 2, pp. 193–200, 1991. View at: Publisher Site | Google Scholar
  17. T. Mader, S. Bundy, and Z. B. Popovic, “Quasi-optical VCOs,” IEEE Transactions on Microwave Theory and Techniques, vol. 41, no. 10, pp. 1775–1781, 1993. View at: Publisher Site | Google Scholar
  18. R. A. York and R. C. Compton, “Quasi-optical power combining using mutually synchronized oscillator arrays,” IEEE Transactions on Microwave Theory and Techniques, vol. 39, no. 6, pp. 1000–1009, 1991. View at: Publisher Site | Google Scholar
  19. J. C. Wiltse and J. W. Mink, “Quasi-optical power combining of solid-state sources,” Microwave Journal, vol. 144, pp. 147–150, 1992. View at: Google Scholar
  20. H. D. Hristov, I. P. Gatzov, J. R. Urumov, G. S. Kirov, and T. G. Ivanov, “Some experiences with resonant cavity antennas-oscillators,” in Proceedings of the IEEE Antennas and Propagation International Symposium, pp. 376–381, Ann Arbor, Mich, USA, July 1993. View at: Google Scholar
  21. L. A. Weinstein, Open Resonators and Open Waveguides, Golem Series in Electromagnetics, Golem Press, 1969.
  22. R. A. York, R. D. Martinez, and R. C. Compton, “Active patch antenna element for array applications,” Electronics Letters, vol. 26, no. 3, pp. 494–495, 1990. View at: Google Scholar
  23. E. Holtzman and R. Robertson, Solid-State Microwave Power Oscillator Design, Artech House, 1992.

Copyright © 2014 L. A. Haralambiev and H. D. Hristov. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

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