Recent Advances in Design and Signal Processing for Antenna Arrays
View this Special IssueResearch Article  Open Access
Ying Suo, Wei Li, Jianzhong Chen, "A SIW Antipodal Vivaldi Array Antenna Design", International Journal of Antennas and Propagation, vol. 2016, Article ID 9280234, 10 pages, 2016. https://doi.org/10.1155/2016/9280234
A SIW Antipodal Vivaldi Array Antenna Design
Abstract
A kind of compact SIW (substrate integrated waveguide) Vivaldi array antenna is proposed and analyzed. The antenna consisted of 4 Vivaldi structure radiation elements fed by an equal power divider with SIW technology. The radiation element is composed of antipodal index gradient microstrip lines on both sides of the substrate. The measured reflection coefficient of the array antenna is less than −10 dB from 8.88 GHz to 10.02 GHz. The measured gain of the array antenna is 13.3 dB on 9.5 GHz.
1. Introduction
The Vivaldi antenna has been used in many microwave engineering applications for its simple structure, low cross polarization, and highly directive patterns characteristics, especially in ultra bandwidth applications such as vehicular wireless communication, radar imaging, and throughthewall imaging [1–3]. Many kinds of Vivaldi antennas have been investigated for wideband application [4, 5], and some new antipodal Vivaldi antennas have been designed to improve radiation pattern and directivity [6, 7].
An equal power divider is necessary for the antenna array feed network for equal amplitude design. The SIW multiway microwave power divider attracts a lot of attentions because of its advantages such as small structural dimension, high integration, and low cost [8–10]. A Vivaldi antenna array fed by a SIW printed on a thick substrate is proposed in [11]. A compact fourelement printed Vivaldi array is designed and investigated in [12].
The SIW is able to be fabricated by standard low cost PCB technique using low loss and low cost material substrates [13]. There is often a higher return loss in an array antenna system than a single antenna one as the feeding network for an array antenna, such as Tjunction or Yjunction waveguide, will introduce a discontinuity where reflection increases sharply. To reduce the return loss, many approaches have been proposed. Reference [14] focused on the structure of its linear tapered array antennas, compared the reflection coefficients of three different structures of the array antenna, and found a maximum −10 dB bandwidth of 0.8 GHz in band, though the bandwidth is not wide.
To broaden the bandwidth of the array antenna, a Vivaldi array antenna operating in band is designed and measured in this paper. Return loss is optimized in both antenna and feed network. Vivaldi antenna is used as the array antenna element for enlarging the bandwidth. To reduce the return loss, metal viaholes are added and adjusted in the SIW. The antenna consisted of 4 Vivaldi antenna elements fed by a SIW equal power divider. Each Vivaldi element is composed of antipodal index gradient microstrip lines on both sides of the substrate, and SIWmicrostrip transition structure is designed for measurement and connection. Finally this paper achieved an antenna design operating in band.
2. 4Way SIW Power Divider Design
A SIW is composed of two columns of cylinder metal viaholes in the side faces of a dielectric substrate and metal layers on the upper and lower faces. The transmission characteristics of a SIW are almost the same as those of its equivalent metal waveguide. As SIWs are often integrated with coplanar waveguides or microstrip lines, transition structures should be designed for the connection. The transition structure must have a low insertion loss, a wide working band, and a simple geometry to be fabricated. The SIW connected with the microstrip transition is shown in Figure 1.
In Figure 1, is the distance between the two columns of cylinder metal viaholes in the SIW, is the distance between viaholes in the viaholes array. Since the field of the microstrip line is similar to the TE10 mode of the substrate integrated waveguide, the SIWmicrostrip transition is generally a tapered microstrip line. The tapered line shown in Figure 2 is able to realize impedance transformation between the 50 Ω microstrip line and the substrate integrated waveguide.
As the tapered line is designed to realize impedance transformation, the left width of the tapered line should equal the width of the 50 Ω microstrip line. The right width of the tapered line should ensure that the impedance of the microstrip line equals that of the SIW.
For the microstrip line, as is shown in Figure 3, its width is ; thickness is ; when the thickness of the dielectric is , the relative permittivity is .
The impedance of the microstrip line will bewhere
The equivalent impedance of the SIW in its TE mode is
Ordinary Yshaped structure can achieve the power division, but its discontinuous geometry will result in high return loss in pass band. Figure 4 shows that a 4way SIW equal power divider is designed. The parameters of the fourway SIW power splitter are shown in Table 1. As is shown in Figure 4, adding a metal viahole in the 90degree bend of the SIW can reduce the power reflection when the electric field distribution of the Yjunction is changed by surface current distribution of the metal viahole inductance. By adjusting the diameter and position of the viahole, the least reflection can be obtained after simulation.

For parameters in Figure 4, is the diameter of the viaholes, is the width of the connection structure, is the width of the first section of Yjunction structure, is the width of the second Yjunction structure, is the thickness of the dielectric slab, and is the thickness of PEC in the simulation setting. It can be seen that , , , and are the diameters of the inductive viahole while , , , , , and determine the position of the viaholes. One viahole is on the perpendicular bisector of the entire structure and the other two viaholes are on the perpendicular bisectors of the two upper Yjunctions, so there are no parameters and .
To be tested by coaxial cable, five SIW microstrip transitions are connected with the SIW power splitter. The parameters of the microstrip transitions mentioned above are , , and . equals 2 and equals 3.2, which ensures the impedance transformation of the 50 Ω microstrip line and the SIW. is optimized to 4.5 for the least reflection loss.
After all the viaholes get their optimized diameter and position that are shown in Table 1, the 4way SIW power divider is simulated. The permittivity of the substrate is 4.3, and the loss tangent is 0.0015 as used in this design. The simulated parameters of different ports are shown in Figure 5. It can be seen that the parameter is less than −10 dB from 8.5 GHz to 10.5 GHz. In Figure 5, the transmission coefficient of , , , and is the same for the equal power division. As shown in Figure 5, the transmission coefficient of the power divider is −6.3 dB~−6.6 dB from 8.9 GHz to 10.07 GHz, so it is suitable for the 4element antenna array design, and the insertion loss is about 0.3~0.6 dB from 8.9 GHz to 10.07 GHz.
The simulated surface current of the SIW divider on 9.5 GHz is shown in Figure 6. And the simulated electric field of the SIW divider on 9.5 GHz is shown in Figure 7.
(a) Phase is 0 deg
(b) Phase is 90 deg
(a) Phase is 0 deg
(b) Phase is 90 deg
3. Antipodal Vivaldi Antenna Array Design
The antipodal Vivaldi radiation element is composed of complementary structures on both sides of the substrate. The antenna element is shown in Figure 8. The upper part is the antenna radiator, the middle part is the connection structure, and the lower part is the microstrip transition. For the upper radiation part of the antenna shown in Figure 8(a), the radiator is bordered by part of an ellipse curve on the right and an index gradient curve on the left. The index gradient curve whose exponential rate equals 1 satisfies the following formula:
(a) Upper part
(b) Lower part
The Vivaldi antenna is directly fed by a microstrip line. Impedance of the microstrip is equal to that of each export of the equal power divider. A SIWmicrostrip transition structure is designed for measurement and connection. The transition section is a tapered microstrip line.
As is shown in Figure 8, is the antenna width, is the antenna length, is set for the length of straight part in SIWmicrostrip transition, is the length of the connection part, and is the length of the radiator. is length of the truncated elliptic curve. The parameters of the Vivaldi radiation element are shown in Table 2.

Parameters on Table 2 are also optimized to get the best radiation characteristics of the antenna. The simulation model of antipodal Vivaldi antenna based on 4way SIW power divider is shown in Figure 9. The dielectric substrate has a relative permittivity of 4.5 and a thickness of 1.6 mm. Parameters of the antenna and the SIW equal power divider equal those in Tables 1 and 2.
(a) Upper part
(b) Lower part
To get the optimized parameters of the diameter and position of a viahole, of the 4way SIW power divider is simulated when one of the parameters of the viahole varies. Because of the symmetry of the SIW, 4 of the 9 viaholes need to be analyzed.
Figure 10 shows the simulated when the diameter of viahole 1 varies from 0.3 to 0.6. It can be seen that the curve moves up when increase, but not very much. Then 0.5 is picked as the optimized value of based on the curves.
when varies from 3 to 6 is shown in Figure 11. In Figure 11, the curve firstly moves down and then moves up as increases. Therefore the optimized lies between 4 and 5. Obviously is vastly dependent on , so repeated simulations were carried out for the least reflection, which have ultimately shown that 4.9 is the best value.
Figure 12 has shown the simulated curves when the diameter of viahole 2 varies from 0.2 to 0.6. The is also not very dependent on . For both low reflection loss and wide bandwidth, 0.5 is picked as .
when varies from 3 to 6 is shown in Figure 13. When increases, the curve firstly moves down and then moves up, but the two resonate frequencies of the curve moves right continuously. In consideration of both bandwidth and center frequency, is chosen.
Simulated is shown in Figure 14 when varies from 3 to 6. As increases, the two center frequencies are moving left. The optimized lies between 4 and 6. After repeated simulation, 5.5 is found to be the optimized .
when varies from 0.3 to 0.6 is shown in Figure 15. The curve is much more dependent on than and , which moves down as increases. 0.5 is picked as the optimized .
when varies from 3 to 6 is shown in Figure 16. The curve firstly moves down and then moves up, but the two center frequencies keep moving right, as increases. 4 is picked as the value of .
Figure 17 shows the curves of the SIW when the diameter of viahole 4 varies from 0.3 to 0.6. The high frequency part of the curve moves up while the low frequency part moves down as increases. So 0.3 is picked as the optimized for wider bandwidth.
when varies is shown in Figure 18. The curve firstly moves down and then moves up as increases. The optimized lies between 7 and 8. Later simulations have found that 7 is the optimized .
when varies from 3 to 6 is simulated and shown in Figure 19. The bandwidth of the curves changes a little while the center frequencies change more when increases. So 4 is picked as the value of in consideration of the two center frequencies.
As is shown in Figure 20, a 4element antipodal SIW Vivaldi antenna array is fabricated and measured. The total dimension of the antenna array is 85 mm × 7 mm with the feeding cable head. The parameters of the antenna array are mm, mm, mm, mm, mm, mm, mm, mm, and mm.
Figure 21 shows the simulated and measured reflection coefficient. Simulated results show that the reflection coefficient is less than −10 dB from 8.9 GHz to 10.07 GHz. And the measured reflection coefficient is less than −10 dB from 8.88 GHz to 10.02 GHz. The measurement shows agreement with the simulation.
The simulated surface current of the SIW Vivaldi antenna array on 9.5 GHz is shown in Figure 22. And the simulated electric field of the SIW Vivaldi antenna array on 9.5 GHz is shown in Figure 23.
(a) Phase is 0 deg
(b) Phase is 90 deg
(a) Phase is 0 deg
(b) Phase is 90 deg
The simulated and measured radiation patterns on 9.5 GHz of the SIW Vivaldi antenna array are shown in Figure 24. The array gain can reach 14 dB on 9.5 GHz in simulation, and the main lobe width is about 17.3°. The measured gain is about 13.3 dB, and the main lobe width is about 16.9°.
(a) Eplane
(b) Hplane
Figure 25 is the simulated gain in operating band. It is shown that the gain is increased with frequency increasing.
4. Conclusion
A 4way SIW equal power divider is designed, and the impedance characteristics and transmission characteristics satisfy the array design. The Vivaldi radiation element consisted of the antipodal structure. The operating bandwidth of the SIW Vivaldi array antenna is more than 1.1 GHz in band. And the gain of the array antenna is 13.3 dB on 9.5 GHz.
Conflict of Interests
The authors declare that there is no conflict of interests regarding the publication of this paper.
Acknowledgment
The authors would like to express their sincere gratitude to funds supported by “the National Natural Science Funds” (Grant no. 61501145).
References
 S. H. He, W. Shan, C. Fan, Z. C. Mo, F. H. Yang, and J. H. Chen, “An improved vivaldi antenna for vehicular wireless communication systems,” IEEE Antennas and Wireless Propagation Letters, vol. 13, pp. 1505–1508, 2014. View at: Publisher Site  Google Scholar
 X. Zhuge and A. G. Yarovoy, “A sparse aperture MIMOSARbased UWB imaging system for concealed weapon detection,” IEEE Transactions on Geoscience and Remote Sensing, vol. 49, no. 1, pp. 509–518, 2011. View at: Publisher Site  Google Scholar
 F. Fioranelli, S. Salous, I. Ndip, and X. Raimundo, “Throughthewall detection with gated FMCW signals using optimized patchlike and Vivaldi antennas,” IEEE Transactions on Antennas and Propagation, vol. 63, no. 3, pp. 1106–1117, 2015. View at: Publisher Site  Google Scholar  MathSciNet
 J. D. S. Langley, P. S. Hall, and P. N. Newham, “Novel ultrawidebandwidth Vivaldi antenna with low crosspolarisation,” Electronics Letters, vol. 29, no. 23, pp. 2004–2005, 1993. View at: Publisher Site  Google Scholar
 R. Natarajan, J. V. George, M. Kanagasabai, and A. Kumar Shrivastav, “A compact antipodal Vivaldi antenna for UWB applications,” IEEE Antennas and Wireless Propagation Letters, vol. 14, pp. 1557–1560, 2015. View at: Publisher Site  Google Scholar
 G. Teni, N. Zhang, J. Qiu, and P. Zhang, “Research on a novel miniaturized antipodal vivaldi antenna with improved radiation,” IEEE Antennas and Wireless Propagation Letters, vol. 12, pp. 417–420, 2013. View at: Publisher Site  Google Scholar
 A. M. De Oliveira, M. B. Perotoni, S. T. Kofuji, and J. F. Justo, “A palm tree antipodal vivaldi antenna with exponential slot edge for improved radiation pattern,” IEEE Antennas and Wireless Propagation Letters, vol. 14, pp. 1334–1337, 2015. View at: Publisher Site  Google Scholar
 S. Germain, D. Deslandes, and K. Wu, “Development of substrate integrated waveguide power dividers,” in Proceedings of the IEEE Canadian Conference on Electrical and Computer Engineering (CCECE '03), vol. 3, pp. 1921–1924, Montreal, Canada, May 2003. View at: Publisher Site  Google Scholar
 Z. Hao, W. Hong, H. Li, H. Zhang, and K. Wu, “Multiway broadband substrate integrated waveguide (SIW) power divider,” in Proceedings of the IEEE Antennas and Propagation Society International Symposium, pp. 639–642, IEEE, July 2005. View at: Publisher Site  Google Scholar
 X. Zou, C.M. Tong, and D.W. Yu, “Yjunction power divider based on substrate integrated waveguide,” Electronics Letters, vol. 47, no. 25, pp. 1375–1376, 2011. View at: Publisher Site  Google Scholar
 S. Yang, A. Elsherbini, S. Lin, A. E. Fathy, A. Kamel, and H. Elhennawy, “A highly efficient Vivaldi antenna array design on thick substrate and fed by SIW structure with integrated GCPW feed,” in Proceedings of the IEEE Antennas and Propagation Society International Symposium, pp. 1985–1988, IEEE, Honolulu, Hawaii, USA, June 2007. View at: Publisher Site  Google Scholar
 L. Bin, D. Liang, and Z. JiaoCheng, “The research of broadband millimeterwave Vivaldi array antenna using SIW technique,” in Proceedings of the International Conference on Microwave and Millimeter Wave Technology (ICMMT '10), pp. 997–1000, IEEE, Chengdu, China, May 2010. View at: Publisher Site  Google Scholar
 W. M. Abdel Wahab, D. Busuioc, and S. SafaviNaeini, “Low cost planar waveguide technologybased dielectric resonator antenna (DRA) for millimeterwave applications: analysis, design, and fabrication,” IEEE Transactions on Antennas and Propagation, vol. 58, no. 8, pp. 2499–2507, 2010. View at: Publisher Site  Google Scholar
 L. Wang, X. Yin, and H. Zhao, “A planar feeding technology using phaseandamplitudecorrected SIW horn and its application,” IEEE Antennas and Wireless Propagation Letters, vol. 14, pp. 147–150, 2015. View at: Publisher Site  Google Scholar
Copyright
Copyright © 2016 Ying Suo et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.