Journal of Electrical and Computer Engineering

Volume 2014 (2014), Article ID 195650, 8 pages

http://dx.doi.org/10.1155/2014/195650

## Joint DOA and DOD Estimation in Bistatic MIMO Radar without Estimating the Number of Targets

^{1}School of Information and Electrical Engineering, Hunan University of Science and Technology, Xiangtan 411201, China^{2}School of Information Science and Engineering, Hunan International Economics University, Changsha 410205, China

Received 18 August 2014; Accepted 22 November 2014; Published 9 December 2014

Academic Editor: Sven Nordholm

Copyright © 2014 Zaifang Xi et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

#### Abstract

Existing subspace-based direction finding methods for multiple-input multiple-output (MIMO) radar assume perfect knowledge about the dimension of the signal or noise subspace, which is hard to be established without prior knowledge of the signal environment. In this paper, an efficient method for joint DOA and DOD estimation in bistatic MIMO radar without estimating the number of targets is presented. The proposed method computes an estimate of the noise subspace using the power of R (POR) technique. Then the two-dimensional (2D) direction finding problem is decoupled into two successive one-dimensional (1D) angle estimation problems by employing the rank reduction (RARE) estimator.

#### 1. Introduction

MIMO radar employs multiple transmit antennas for transmitting several orthogonal waveforms and multiple receive antennas for receiving the echoes reflected by the targets [1–3]. MIMO radar can exploit the waveform diversity to form a virtual array with increased degrees of freedom (DOFs) and a larger aperture compared to the traditional phased-array radar. It has been shown that MIMO radar can provide enhanced spatial resolution, achieve better target detection performance, and significantly improve the system’s parameter identifiability [1–6].

Many direction finding methods have been proposed (see [7–11] for details) for MIMO radar. In [9], the estimation of signal parameters via rotational invariance technique (ESPRIT) was used for angle estimation in bistatic MIMO radar. The multiple signal classification (MUSIC) [12] algorithm, one of the most representative subspace methods, can also be used for direction finding in bistatic MIMO radar. However, the requirement of 2D search of 2D-MUSIC for spectral peaks leads to much higher computational complexity. To mitigate this problem, many joint DOA and DOD estimation methods have been proposed (see [8, 10, 11] for details). The aforementioned direction finding methods for bistatic MIMO radar are based on the noise or signal subspace. Thus, the number of targets, that is, the dimension of the signal subspace, has to be known* a priori*. The most representative algorithms for estimating the number of sources are Akaike information criterion (AIC) and minimum description length (MDL) [13]. However, experimental evidence shows that the two criteria cannot give accurate estimation results for a small sample size and a low signal-to-noise ratio (SNR) [14–16]. Hence, the existing subspace-based direction finding methods for bistatic MIMO radar may be unrealistic. To avoid source number estimation, in [17], the Capon estimator of [18] was used for direction finding in MIMO radar. However, the Capon estimator cannot achieve resolution as high as that of the MUSIC algorithm [13].

In this work, we address the problem of joint DOA and DOD estimation in bistatic MIMO radar without estimating the number of targets. To eliminate the need to estimate the dimension of the noise subspace explicitly, the POR technique is employed to compute an estimate of the noise subspace. The POR technique requires the inverse of the sample covariance matrix. Due to finite sample effect, however, the sample covariance matrix may be either singular or ill-conditioned. To guarantee that the sample covariance matrix is invertible, a completely automatic diagonal loading (ADL) method introduced in [19], which computes the diagonal loading (DL) level automatically from the received data without specifying any user parameter, is utilised to estimate a well-conditioned sample covariance matrix. In addition, based on the RARE estimator for direction finding in partly calibrated arrays [20], the 2D angle estimation problem is then decoupled into two successive 1D angle estimation problems.

This paper is organised as follows. In Section 2, the signal model for bistatic MIMO radar is provided. In Section 3, a brief overview of 2D-MUSIC, ESPRIT, and reduced-dimension MUSIC (RD-MUSIC) for direction finding in bistatic MIMO radar is given. The proposed method is given in Section 4. Simulation results are presented in Section 5 and conclusions are drawn in Section 6.

#### 2. Signal Model for Bistatic MIMO Radar

Consider a bistatic MIMO radar system with a ULA of antennas used for transmitting and a ULA of antennas used for receiving. The transmit antennas are used to transmit orthogonal waveforms. Consequently, the output of the matched filters of MIMO radar at the th snapshot can be written as [4, 8]: where are the DOAs and DODs of the targets with respect to the receive array normal and transmit array normal, respectively; stands for the Kronecker product operator, ; are the transmit and receive steering vectors for and , with and , where and are the interelement spacings of the transmit and receive arrays and is signal wavelength; , with being the complex-valued reflection coefficient of the th target and being Doppler frequency; ; is the overall transmit-receive or virtual array manifold, and is the received complex-valued white noise with a power .

Due to the time-varying properties of the reflection coefficients and the fact that the Doppler frequencies satisfy and are well-separated, we assume that all target-reflected signals and noise are uncorrelated. Then the data covariance matrix can be expressed as where and denote expectation and Hermitian transpose, respectively; is the signal covariance matrix, with being the variance of the th source; is the identity matrix, consists of the principal eigenvalues of , is the signal subspace, specified by the principal eigenvectors of , and the remaining eigenvectors are the noise subspace. In practice, the sample covariance matrix of (4), is used, where is the number of snapshots.

#### 3. Review of 2D-MUSIC, ESPRIT, and RD-MUSIC

##### 3.1. 2D-MUSIC

The 2D-MUSIC algorithm can be constructed as [8]: The largest peaks of indicate the DOA and DOD estimates of the targets. 2D-MUSIC algorithm requires a 2D search, which yields a high computational cost.

##### 3.2. ESPRIT

For ESPRIT-based estimator [9], it is based on the signal subspace . Let be the subset of , which relates from the first to the th transmit antennas, and be the subset of , which relates from the second to the th transmit antennas. We then have the following relationship: where is an unknown nonsingular matrix and is a diagonal matrix, with being its th main diagonal element. Thus, the DODs can be found from the eigenvalues of . Similarly, by using the rotational invariance property between the receive steering vectors associated with the first and last antennas, the DOAs can be obtained easily using the ESPRIT-based method.

##### 3.3. RD-MUSIC

To reduce the computational complexity of the 2D-MUSIC algorithm, the RD-MUSIC algorithm was proposed [8]: where and is the vector.

Using the Lagrange method, the solution to the problem (8) is given by Substituting of (9) into , the DOAs can then be estimated via The largest peaks of indicate the DOAs, and we also obtain vectors according to (9). Using the obtained , we can compute the DOD estimate corresponding to each DOA estimate of (see [8] for details).

The RD-MUSIC undergoes the following limitations. First, the RD-MUSIC fails when multiple targets share the same DOA but have different DODs. Second, it cannot be always guaranteed that the matrix is invertible. It can be proved that the matrix may be either singular or ill-conditioned.

*Proof. *In the ideal case of exactly known , the DOAs and DODs can be found from the following equation:
Since , (11) can hold true only if the matrix drops rank; that is,
From the above analysis, it follows that the matrix may be either singular or ill-conditioned. Therefore, a small DL factor should be loaded into to guarantee that it is invertible.

#### 4. Proposed Method

##### 4.1. Estimating Noise Subspace

To avoid the need of source number estimation, the POR technique estimates the noise subspace of based on [21]. Consider the following equation: where is a positive integer. Clearly, is less than 1; thus converges to zero for sufficiently large . Theoretically, we have [21]: Therefore, the POR technique obtains an estimate of the noise subspace without knowledge about the number of targets.

It should be noted that the POR technique is not applicable when , because if snapshots are used to form , eigenvalue estimates are zero [22]. In such a case, is rank deficient and is not invertible. To overcome this problem, we suggest using the ADL method introduced in [19] to estimate an enhanced covariance matrix. The essence behind the ADL is to replace the sample covariance matrix by an enhanced estimate obtained via a shrinkage method. The shrinkage-based covariance matrix estimate is a general linear combination of the sample covariance matrix and the identity matrix [19, 23]: where and are the enhanced estimate and sample estimate of the actual covariance matrix , respectively, and and are the shrinkage parameters, which can be obtained by minimising the mean-squared error (MSE) of : where and denote the trace operator and the Frobenius norm, respectively. As suggested in [19, 23], the estimates of and can be obtained as where

##### 4.2. Performing Angle Estimation

Substituting into (11) to replace , we have

Since , (19) holds true only if the matrix drops rank so that Note that if , that is, , in general, is a full rank, and the reduction of the rank of will take place on the true DOAs [20]. In this case, the minimal eigenvalue of will tend to have a minimum when coincides with one of the DOAs , [24]. Therefore, the highest peaks of indicate the DOAs, where denotes the operator that yields the minimal eigenvalue of a matrix.

After obtaining the DOA estimates, we then utilise an appropriate modification of the spectral MUSIC algorithm to obtain the DOD estimates. By exploiting the DOA estimates given by (21), the corresponding DODs can be estimated from the highest peaks of the following function: It is worth noting that two successive 1D searching are required only for finding the angle estimates of , leading to significant reduction of its computational cost compared with the traditional 2D spectral searching algorithms.

##### 4.3. Cramér-Rao Bound

In this subsection, we derive the stochastic Cramér-Rao bound (CRB) for joint DOA and DOD estimation by extending the results of [20].

Define the vector containing the unknown parameters, where

The snapshots are assumed to satisfy the following stochastic model: where is the complex Gaussian distribution. The unknown parameters of the problem include the elements of the vector , the noise variance , and the parameters of the source covariance matrix and .

Considering the problem with respect to the parameters of the source covariance matrix and the noise variance, the Fisher information matrix can be written as [20]: where is the orthogonal projection matrix and the matrix After straightforward derivations using (25) and combining them in a compact matrix form, the CRB matrix can be expressed as where denotes the Schur-Hadamard matrix product and is the vector of ones. Here, the matrix is defined as where

#### 5. Simulations

In this section, simulations are carried out to investigate the performance of the proposed method compared with the 2D-MUSIC, ESPRIT-based of [9], RD-Capon of [17], and the RD-MUSIC of [8]. We consider a bistatic MIMO radar system where a ULA of antennas is used for transmitting and a ULA of antennas is used for receiving. Both of these ULAs are arranged with half-wavelength spacing between adjacent antennas. Three noncoherent targets with the same signal-to-noise ration (SNR) are located at angles , , and , respectively. The additive noises are spatially and temporally white. The input SNR of the th source is defined as . All results are averaged over 500 simulation runs. Define the root mean squared error (RMSE) as where is the estimate of DOA/DOD of the th run.

Figure 1 shows the effect of the parameter on the performance of the proposed method for . As shown, the proposed method with a small has better estimation accuracy at the low SNR region. As the input SNR increases, the proposed method with a large outperforms the one with a small . Figure 2 presents the spatial spectrum of DOA estimation of the RD-MUSIC, the RD-Capon, and the proposed method. It can be clearly seen that the proposed method with and the RD-MUSIC achieve similar resolution, which is higher than that of the RD-Capon. From the results of Figures 1 and 2, in the following examples we will choose for the proposed method.