Research Article  Open Access
Composite Broadcasting and Ranging via a Satellite DualFrequency MPPSK System
Abstract
Since digital video broadcasting via satellite (DVBS) signals are “inefficient”, regarding the amount of information they convey on the bandwidth they occupy, a joint broadcasting and ranging system would constitute a unique platform for future digital video broadcasting satellite services effecting the essential tasks of satellite navigation system and direct to home (DTH) services, in terms of both spectrum efficiency and cost effectiveness. In this paper, the design of dual frequency Mary position phase shift keying (MPPSK) system which is suitable for, respectively, performing both data transmission and range measurement is proposed. The approach is based on MPPSK modulation waveforms utilized in digital video broadcasting. In particular, requirements that allow for employing such signals for range measurements with high accuracy and high range are investigated. Also, the relationship between the frequency difference of dual frequency MPPSK system and range accuracy is discussed. Moreover, the selection of MPPSK modulation parameter for data rate and ranging is considered. In addition to theoretical considerations, the paper presents system simulations and measurement results of new systems, demonstrating the high spectral utilization of integrated broadcasting and ranging applications.
1. Introduction
Direct to home (DTH) services via satellite are particularly affected by power limitation, which weakens its ability of antinoise and antiinterference. Traditionally, power limitation is the main design objective rather than spectrum efficiency, so DVBS system uses QPSK modulation [1]. However, the spectrum resource in the air has become more occupied, with rapid development of digital video and audio broadcasting. To achieve a very high spectrum efficiency without excessively penalizing the power efficiency, the modulation technique named Mary position phase shift keying (MPPSK) was proposed, which is a kind of transmission technique with efficientbandwidth and high data rate [2, 3].
Compared to EBPSK [4], MPPSK utilizes Mary information symbols to directly control the positions of phase transition of sinusoidal carrier in each symbol cycle. These techniques offer a number of advantages, such as ultranarrow bandwidth, very high transmission efficiency, and adjustable data rate. Different from QPSK, MPPSK preserves a strong carrier within its RF spectra, because only a small portion of sine carrier is changed. Meanwhile, the receiver can extract the tiny modulation information to achieve demodulation while applying an extremely narrow passband filter named digital impacting filter (DIF). References [5, 6] explained the special mechanism of DIF elaborately. Continuous wave (CW) ranging has been demonstrated potential for providing precise detection results; however, they suffer from large range ambiguity [7]. Dual frequency CW ranging has a contradiction between the accuracy and range of measurement [8, 9].
In the paper, a dual frequency MPPSK system is creatively proposed to overcome the ranging ambiguity. At the same time, the system is used for the digital video broadcasting satellite services. Such a kind of platform would offer unique possibilities for novel system concepts and applications. Even more important, by using the dual frequency MPPSK waveform for both applications, the occupied spectrum would be used very efficiently and both applications could be operated, respectively, which would guarantee availability of both functions, and help to partially overcome the limitation of spectral resources. Such a system will provide two functions on a single hardware platform of MPPSK modems.
The rest of this paper is organized as follows: Section 2 introduces MPPSK modulation and demodulation, including the waveform character and the performance of impacting filters. Section 3 illustrates principle of dual frequency CW ranging. In Section 4, a block diagram of the dual frequency MPPSK broadcasting and receiving system is partly described, and also, two working modes are established. Some indicative simulation results and performance analysis are presented in Section 5. And finally, Section 6 gives the conclusion of the paper.
2. MPPSK Modem
2.1. MPPSK Modulation
The modulated MPPSK signals are defined by [2], and the simplified expression is presented in the paper as follows: where and represent the carrier frequency and the carrier period, respectively. and stand for the number of the carrier period in each time slot and the number of the carrier period in each symbol, respectively. means the slot number in each symbol, and is Mary source symbol. The waveforms of 4PPSK modulation are illustrated as in Figure 1. The coefficient for the abscissa axis is the index of a certain sample point. Setting , .
The modulation waveform for symbol “0” is sinusoidal wave as shown in Figure 1. Figure 1 also illustrates the modulation waveform for symbol “1” with the phase hopping during the first two carrier period (from 0 to 20), the next (from 20 to 40) is for symbol “2”, and last (from 40 to 60) is 3 for symbol “3”.
MPPSK modulation generator is a new analogdigitalmixed type. Pulse train MPPSK modulator is illustrated by [3]. The modulating process of 4PPSK signal in carrier frequency is shown in Figure 2.
The next step is to explain the processes more clearly, and the output of a sinewave oscillator with frequency is divided into two branches: the upper is direct output with no phase shift, while the lower is phase reversed before output. The original data sequence to be transmitted is converted into a corresponding impulse chain firstly so as to control an electronic switch . By (1), this chain always stays at low level (logic “0”) except for the beginning of bit “” () and during the interval of where the impulse appears and stays at high level (logic “1”). Controlled by this information impulse chain, the is connected to at low level, to at high level.
2.2. MPPSK Demodulation
The impacting filter (IF) is a special digital infinite impulse response (IIR) filter, with the feature of “notchfrequency selection” in an extremely narrow passband [6]. It highlights the difference of the modulation waveform, which is helpful for demodulation, and simplifies the structure of the receiver greatly. At present, the IF is artificially designed. In the following real simulation, we assume the impacting filter formed by one pair of conjugate zeros and four pairs of adjacent conjugate poles. The expression and related parameter of the IF is given in [10].
Consider where is the pair number of the conjugate poles. In order to demodulate dualfrequency MPPSK signals, the zero parameters of the IF are selected as , and the pole parameters of the IF in this paper are selected as The proposed filter has a very narrow bandwidth, and the IF would retain the signal characteristics and reduce the noise. When MMPSK modulated signals pass the impacting filter, the special impacting filter can transform the tiny waveform difference into amplitude impacting, and Figure 3 would illustrate this demodulation process.
The coefficient for the axis is the index of a certain sample point. Set MPPSK Modulation parameter . Waveform of a source symbol sequence is shown in Figure 3, Figure 3 illustrates its 4PPSK waveform after the modulation, Figure 3 depicts the response of this filter to 4MPSK modulated signals, the phase hopping can be converted into amplitude impacting, and its envelope is shown in Figure 3.
Nonzero symbols, that is, “1” to “”, can be distinguished from the different positions of the peak of amplitude impacting. Figure 3 shows the waveform corresponding to four symbols, “3”, “2”, “1”, and “0.” The modulation waveform for symbol “0” is a sinusoidal. Therefore, no impacting is observed in its response. The peak of amplitude impacting (at about in Figure 3) corresponding to code “1” is close to the starting location (at about in Figure 3). The followed modulation waveform is for code“2” (at about in Figure 3), which is a little further from its own starting location (at about in Figure 3). And the last is for code “3” (at about in Figure 3), which is the furthest from its own starting location (at about in Figure 3). Obviously, a simple amplitude threshold detector and bit synchronization can perform the demodulation for MPPSK signals, which results in the simple receiver structure. The impacting filter can be digitally implemented, which is beneficial for chip integration.
3. Dual Frequency CW Ranging
Dual frequency CW ranging technique can compute very adequate fine range resolution [11, 12], without using frequency modulation. Consider a CW signal of single frequency first: where is the carrier frequency and . The receiver’s range and is computed by measuring the time delay , it takes CW signal to travel the path between transmitter and receiver. Since electromagnetic waves travel at the speed of light , the received signal is where the time delay .
Solving for , we obtain
Such a system with zerointermediate frequency (ZIF) receiver is shown in Figure 4. PA stands for power amplifier and LNA represents lownoise amplifier; orthogonal channel is used in radar receiver for obtaining echo reflected signal phase and amplitude information. Clearly, the maximum unambiguous range occurs when is maximum; that is, . Consider a system with two CW signals, denoted by and , respectively. More precisely, The received signals from transmitter are where and .
After heterodyning (mixing) with the carrier frequency, the phase difference between the two received signals is where and .
Again is maximum when ; however, at this circumstance, the maximum unambiguous range is In practice, besides the carrier frequency difference , range resolution depends on SNR [13], approximately wavelength, which is larger than the ideally achievable value. Then the range resolution can be Ambiguity may occur in range measurement especially when carrier frequency difference is high or the receiver’s range is longer than . From (10) and (11), achieving fine range resolution can be accomplished by increasing frequency different , but maximum unambiguous ranging is decreasing. The limited ranging measurement also limits the actual application value of dual frequency CW radar.
4. Dual Frequency MPPSK System Model
4.1. Broadcasting and Ranging Transmitter
Broadcasting and ranging transmitter equipment is mainly composed of two pulse train MPPSK modulation generators, as shown in Figure 5. PA stands for power amplifier.
Two working modes are designed which depend on the original data source. For digital video broadcasting, the data rate and the bit error rate (BER) are the most stringent parameters. Pulse train MPPSK modulator 1 transmits MPPSK signals, which is efficient regarding the amount of information they convey on the bandwidth they occupied. And pulse train MPPSK modulator 2 will stop working when satellite is particularly affected by power limitations.
For the ranging function, the waveform should be robust against interference, noise, and distortion due to multipathpropagation. The pulse train MPPSK modulator 1 transmits MPPSK signals, which are modulated by the original data symbol “1” constantly and is sinelike waveform. Pulse train MPPSK modulator 2 transmits CW, which may be considered to be a special kind of MPPSK signals, the system signals are denoted by .
Consider where and are the carrier frequency, and for , symbol rate is , which is denoted by The power spectral density (PSD) of has been figured out in conditions of “” distributed in equal probability.
Consider where is Fourier transform of MPPSK modulated waveforms corresponding to symbol “”, “”,, “”, respectively.
4.2. Broadcasting and Ranging Receiver
Broadcast and ranging reception equipment is made by two kinds of receivers, and one is mainly composed of phase discriminator (PD), and the other is mainly composed of variable bit rate MPPSK (VBRMPPSK) demodulation. As shown in Figure 6, receiver 1 and receiver 2 have been illustrated in Figure 4, and principle of MPPSK demodulation has been described in Section 2. The MPPSK signal in carrier frequency is demodulated by VBRMPPSK demodulation. The output data can be converted to video after data processing. Signals both in carrier frequency and in carrier frequency are demodulated with PD. The output data combined with would be converted to distance value after data fusion.
Not only the employed waveform but also the general parameters have to be chosen according to the requirements derived from both applications. For broadcasting, digital video signals are demodulated by VBRMPPSK demodulator alone. From (1), the variables , and form a parameter set to adjust the bandwidth, data rate and BER performance. Increasing value of can lead to higher data because more time slots are utilized. While taking multipath channel environment into consideration, large is advantageous in mitigating multipath effect but pulls down the data rate and the efficiency of time slot. Therefore, small values of results in sinelike waveform, which presents in solitudepeak lowsideband PSD apearence and occupies very limited bandwidth. So it is very important to trade off the parameters selection of MPPSK.
For ranging, theoretically, the maximum unambiguous range of MPPSK system must correspond to , which is denoted by and should be chosen according to as So the maximum unambiguous ranging of dual frequency CW ranging system would be increased times as follows: Combining (15) and (16) yields From Figure 6, is highprecision measured value, and is widerange measured value. Combining the two measured values, the system would output a value of with highprecision and widerange; that is, where stands for round up.
Due to the increase in carrier frequency of a CW signal, the dual frequency MPPSK signal becomes synthetical waveforms, that are suitable, respectively, for performing both data broadcasting and ranging. Compared with dual frequency CW ranging technique, the maximum unambiguous range is extended from to .
5. Simulation Results
5.1. Ranging Mode
In this section, the performance of the proposed dual frequency MPPSK system is simulated. Firstly, we consider the dual frequency MPPSK system shown in Figures 5 and 6 in ranging mode. In Table 1, a summary of the most important parameters of the simulation model is provided.

As shown in Figure 7, the left subfigure is the global graph and the right one is the local enlarging graph for the carrier frequencies and . Obviously, the PSD of MPPSK ranging signal has a more narrow bandwidth with 99% power (or −60 dB bandwidth). When turns small, dual frequency MPPSK signal becomes more similar to pure sine waveform. Spectra of the ranging signal from system will be concentrated at carrier frequency and carrier frequency . Smaller portion of the sine carrier can be changed, and the line spectrum components in PSD of the MPPSK modulated signal become lower and even disappear. MPPSK tries to allocate as much power as possible to the carrier.
(a)
(b)
The simulation experiment is in the AWGN channels ( dB), and as shown in Figure 8, the result is output of VBRMPPSK demodulation. The rough range value can be computed by the time delay corresponding to amplitude impacting. The amplitude impacting is at the time delay of 1.9997 ms, and from (15), the rough range value is 599 910 m.
From Figure 9, the simulation result and CR bound just have approximately 0.3 m difference when SNR is 10 dB, with the increase of SNR, difference between simulation result and the theoretical result decreases, and RMS error shrinks towards equality in dB.
5.2. Broadcasting Mode
We also consider the system shown in Figures 5 and 6 in broadcasting mode. In Table 2, a summary of the most important parameters of the simulation model is provided.

Figure 10 shows the PSD of QPSK and proposed MPPSK signal with the same modulation parameters. As shown in Figure 10, the left subfigure is the global graph of the PSD of 8 PPSK and QPSK, and right one is the local enlarged graph nearing the carrier frequency . Obviously, in MPPSK modulation, the line spectra, illustrating the periodic components of the modulated signal, decrease greatly, because of the random choosing of the positions. Therefore, MPPSK becomes more approximate to sine signal, the bandwidth with 99% power (or with −60 dB bandwidth) decreases, and the spectra efficiency is improved greatly.
(a)
(b)
Figure 11 illustrates the SER in different modem, and the simulation shows that at , the SNR performance of the system with MPPSK modem may be improved by approximately 8 dB and 13 dB as compared with the performance of DVBS with QPSK modulation and coherent demodulation and 16QAM modulation and coherent demodulation, respectively.
The result of the dual frequency MPPSK system and single frequency MPPSK system just have less than 1 dB difference in order to obtain the same SER performance, which is caused by the detection method and the selection of the decision threshold in the simulation. Simultaneously, research on the optimal modem method is underway; the system performance still has room for improvement.
6. Conclusions
The SER performance of the dual frequency MPPSK system is better than that of QPSK in such case, and its occupied bandwidth is much narrower than QPSK. QPSK tries to spread as much power as possible to the sidebands. On the opposite side, MPPSK allocates most power in the carrier to keep sideband energy emissions negligible, and dual frequency MPPSK system also provides an augmentation service, that is, the ranging function. After data integration between PD receiver and VBRMPPSK demodulator, system would provide high precision ranging and extend maximum unambiguous range as well. The dual frequency MPPSK system is illustrated in block diagram, which is advantageous MPPSK signal generator and integrated receiver architecture, PD and impacting filter that essentially determine dual frequency signal demodulation are emphasized in the paper and correlation receiver distance simulation are made. The future work will continue with the research on dual frequency MPPSK system, including selection and combinations of other impacting filter and ranging algorithms. Different channel environment profile, as well as channel coding will be further considered.
Acknowledgments
The authors thank all of the reviewers for their valuable comments, which have considerably helped in improving the overall quality of the work presented in the revised paper. This work was supported by the National Natural Science Foundation of China (61271204).
References
 ETSI, “Digital broadcasting systems for television, sound and data service, framing structure, channel coding and modulation for 11/12 GHz satellite services,” ETS 300 421, 1994. View at: Google Scholar
 C. Qi and L. Wu, “PLL demodulation technique for Mray position phase shift keying,” Journal of Electronics, vol. 26, no. 3, pp. 289–295, 2009. View at: Publisher Site  Google Scholar
 P. K. Ying and L. N. Wu, “New scheme of MPPSK modem,” Journal of Southeast University, vol. 42, no. 2, pp. 204–208, 2012. View at: Publisher Site  Google Scholar
 L. Wu and M. Feng, “On BER performance of EBPSKMODEM in AWGN channel,” Sensors, vol. 10, no. 4, pp. 3824–3834, 2010. View at: Publisher Site  Google Scholar
 J. Sun, W. Fang, and W. Xu, “A quantumbehaved particle swarm optimization with diversityguided mutation for the design of twodimensional IIR digital filters,” IEEE Transactions on Circuits and Systems II, vol. 57, no. 2, pp. 141–145, 2010. View at: Publisher Site  Google Scholar
 M. Feng, L. Wu, and P. Gao, “From special analogous crystal filters to digital impacting filters,” Digital Signal Processing, vol. 22, no. 4, pp. 690–696, 2012. View at: Publisher Site  Google Scholar  MathSciNet
 P. van Genderen, “Recent advances in waveforms for radar, including those with communication capability,” in Proceeding of the European Radar Conference (EuRAD '09), pp. 318–325, Rome, Italy, October 2009. View at: Google Scholar
 C. Sturm and W. Wiesbeck, “Waveform design and signal processing aspects for fusion of wireless communications and radar sensing,” Proceedings of the IEEE, vol. 99, no. 7, pp. 1236–1259, 2011. View at: Publisher Site  Google Scholar
 Y. Zhang, M. Amin, and F. Ahmad, “A novel approach for multiple moving target localization using dualfrequency radars and timefrequency distributions,” in Proceeding of the 41st Asilomar Conference on Signals, Systems and Computers (ACSSC '07), pp. 1817–1821, Pacific Grove, Calif, USA, November 2007. View at: Publisher Site  Google Scholar
 M. Feng, L. Wu, J. Ding, and C. Qi, “BER analysis and verification of EBPSK system in AWGN channel,” IEICE Transactions on Communications, vol. E94B, no. 3, pp. 806–809, 2011. View at: Publisher Site  Google Scholar
 Weibel Inc, “Weibel RR60034 ranging radar system”. View at: Google Scholar
 Weibel, “Weibel azimuth & elevation monopulse doppler tracking radar systems,” 1997–2002. View at: Google Scholar
 S. Peleg and B. Porat, “The CramerRao lower bound for signals with constant amplitude and polynomial phase,” IEEE Transactions on Signal Processing, vol. 39, no. 3, pp. 749–752, 1991. View at: Publisher Site  Google Scholar
Copyright
Copyright © 2013 Yu Yao et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.