On the Secrecy Performance of SWIPT Receiver Architectures with Multiple Eavesdroppers

Jameel, Furqan; Wyne, Shurjeel; Junaid Nawaz, Syed; Ahmed, Junaid; Cumanan, Kanapathippillai

doi:https://doi.org/10.1155/2018/8747420

Wireless Communications and Mobile Computing

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Abstract Introduction System Model Discussion Conclusion Conflicts of Interest Acknowledgments References Copyright Related Articles

Research Article | Open Access

Volume 2018 | Article ID 8747420 | https://doi.org/10.1155/2018/8747420

On the Secrecy Performance of SWIPT Receiver Architectures with Multiple Eavesdroppers

Furqan Jameel,¹Shurjeel Wyne,¹Syed Junaid Nawaz,¹Junaid Ahmed,¹and Kanapathippillai Cumanan²

Academic Editor: Gonzalo Vazquez-Vilar

Received04 Dec 2017

Revised16 Apr 2018

Accepted02 May 2018

Published07 Jun 2018

Abstract

Physical layer security (PLS) has been shown to hold promise as a new paradigm for securing wireless links. In contrast with the conventional cryptographic techniques, PLS methods exploit the random fading in wireless channels to provide link security. As the channel dynamics prevent a constant rate of secure communications between the legitimate terminals, the outage probability of the achievable secrecy rate is used as a measure of the secrecy performance. This work investigates the secrecy outage probability of a simultaneous wireless information and power transfer (SWIPT) system, which operates in the presence of multiple eavesdroppers that also have the energy harvesting capability. The loss in secrecy performance due to eavesdropper collusion, i.e., information sharing between the eavesdroppers to decode the secret message, is also analyzed. We derive closed-form expressions for the secrecy outage probability for Nakagami- fading on the links and imperfect channel estimation at the receivers. Our analysis considers different combinations of the separated and the integrated SWIPT receiver architectures at the receivers. Numerical results are provided to validate our analysis.

1. Introduction

Simultaneous wireless information and power transfer (SWIPT) systems have spurred considerable research interest in both academia and industry [1]. The SWIPT technique provides significant convenience to its users by efficiently utilizing the radio frequency (RF) signal for both information and power transfer [2]. However, SWIPT systems require a special receiver design to support the dual capability of energy harvesting (EH) and information decoding (ID). In the literature, two broad categories of SWIPT receiver architectures have been proposed, namely, the separated and the integrated receiver architectures [1]. The separated receiver architecture has dedicated separate units for ID and EH. However, this increases the complexity and cost of the receiver hardware [3]. In contrast, the integrated receiver architecture has a unified circuitry to perform ID and EH jointly, which reduces the hardware costs [3].

Varshney et al. in [4] were the first to propose the transmission of information and energy simultaneously. They developed a capacity-energy function to characterize the fundamental tradeoff in performance between simultaneous information and power transfer. In [5], the authors extended the work of [4] to frequency-selective channels with additive white Gaussian noise (AWGN). It was shown in [5] that a nontrivial tradeoff exists for information transfer versus energy transfer via power allocation. A SWIPT system under cochannel interference was studied in [6]. The authors derived optimal designs to achieve outage-energy tradeoffs and rate-energy tradeoffs. In [7] the authors considered the performance of a SWIPT system with imperfect channel state information (CSI) at the transmitter. Networks that employ pure wireless power transfer were studied in [8, 9]. In [8], the authors studied a hybrid network that overlaid an uplink cellular network with randomly deployed power beacons, which charged mobiles wirelessly. The authors then derived the tradeoffs between different network parameters under an outage constraint on the data links.

The broadcast nature of wireless signals implies that nodes other than the intended receiver may also receive the transmitted message, which results in information leakage. Although cryptography-based techniques are conventionally used to secure transmitted information, the high computational complexity of these techniques consumes a significant amount of energy [10]. Recently, physical layer security (PLS) has been proposed as an alternative for securing wireless communications by exploiting the channel characteristics such as fading, noise, and interferences [11]. The secrecy performance of a cooperative network was investigated in [12, 13]; secrecy for interference limited networks was studied in [14] and for cognitive radio networks in [15–17]. In[18], the authors analyzed the secrecy performance of a multicast network in which the transmitter broadcasted its information to a set of legitimate users in the presence of multiple eavesdroppers. The authors then proposed power minimization and secrecy rate maximization schemes for the considered multicasting secrecy network. The security of large-scale networks has also been characterized in terms of connectivity [19], coverage [20], and capacity [21]. Researchers have also considered so-called artificial noise generation techniques to reduce the signal-to-interference ratio of the eavesdropper channel while minimizing the interference to the legitimate link [22, 23]. The authors in [24, 25] studied cooperative jamming, whereby a relay transmitted an interfering signal towards the eavesdropper while the source broadcasted its message. In [26], secure beamforming techniques have been explored to maximize the received power at the legitimate receiver. The PLS techniques are naturally applicable to SWIPT but the design of an optimal PLS techniques for SWIPT systems is a nontrivial task since it needs to also consider the efficiency of the wireless power transfer. In general, if a power receiver is a potential eavesdropper then any increase in the information signal power to improve the power transfer efficiency may also compromise the message secrecy [6]. Therefore, the inherent tradeoff between power efficiency and information security in a SWIPT system merits detailed examination. The authors in [27] investigated the maximization of secrecy throughput for SWIPT systems. In particular, they considered power allocation between EH and ID to provide an optimal secure SWIPT solution. In the same work an analytical expression for the secrecy outage probability was also derived. In [28], the authors investigated the secrecy performance of a SWIPT system with the separated receiver SWIPT architecture employed at the eavesdropper and faded links. In [29] the authors introduced an artificial noise-aided precoding scheme to maximize the secrecy rate. In [30] the authors studied the secrecy capacity of an EH orthogonal-frequency-division-multiplexing network. All the subcarriers were allocated an identical power and the power-splitting technique was used to coordinate ID and EH. In [31] the authors analyzed secure beamforming for an amplify-and-forward two-way relaying SWIPT network and proposed a zero-forcing based suboptimal solution to maximize the secrecy of the considered network.

In the SWIPT literature most investigations have considered only the separated receiver architecture [27, 29–31]. Furthermore, multiple eavesdroppers when considered are often assumed to operate independently, whereas in many practical scenarios these eavesdroppers may collaborate to enhance their secret message decoding capability [32]. Finally, the achievable secrecy rate may degrade significantly under imperfect channel estimation at the legitimate receiver, whereas imperfect CSI at the eavesdropper can prove beneficial for the system’s secrecy performance. To the best of the authors’ knowledge, a comparative analysis of the secrecy performance of the separated and integrated SWIPT architectures with eavesdropper cooperation and imperfect CSI has not been performed previously. Specifically, the main contributions of the submitted work are listed as follows:(i)We derive closed-form expressions for the secrecy outage probability with imperfect CSI knowledge at the receivers and different combinations of the separated and the integrated SWIPT architectures at the legitimate and eavesdropping receivers.(ii)The tradeoff between secrecy performance and harvested energy is investigated.(iii)The loss in secrecy performance due to eavesdropper cooperation is analyzed and compared with the noncooperative case.

The remainder of this paper is organized as follows. Section 2 presents the system model. In Section 3 the closed-form expressions for the outage probability are derived for different receiver architectures. Section 4 provides numerical results along with relevant discussion. In Section 5, some concluding remarks are given.

2. System Model

We consider the downlink of a SWIPT system as shown in Figure 1 in which the Access Point (AP) transmits a secure message to the legitimate receiver S, which has simultaneous EH and ID capability. This transmission is also received by eavesdropping nodes that are admitted into the network for EH-only but exploit their SWIPT receiver architectures in an attempt to intercept the secret communication between AP and S [33]. Since the eavesdroppers, denoted by , are also part of the network, the AP is assumed to have CSI for the main channel to node S as well as for the wiretap channels [33]. All nodes are considered to be equipped with single antennas (analysis for multiantenna nodes [34] will be reported in future work). Our analysis considers two types of receiver architectures for both S and , i.e., the conventional separated receiver and the integrated receiver architecture [3] shown in Figure 2. In the separated receiver, the RF signal after power-splitting (PS) is fed to separate circuitry for ID and EH, whereas in the integrated receiver PS between EH and ID takes place after the rectifier. The rectifier of the integrated receiver also downconverts the RF signal for ID; i.e., the downconversion operation is integrated with the energy receiver in this architecture. For both receiver types, the fractional powers received for ID and EH are denoted by and , respectively.

Consider that the AP transmits signal with power . The signal received at S can then be written aswhere represents the channel gain estimated by S and denotes the zero-mean variance additive white Gaussian noise (AWGN) due to the receiver electronics at S. Additionally, is the path loss, where denotes the distance between AP and S and is the path loss exponent. Furthermore, is the carrier wavelength and and are the antenna gains at AP and S, respectively.

Since S employs PS architecture, the received signal is further divided into two streams for ID and EH. The signal at the information decoder of S is given aswhere is the power-splitting factor at S and is the signal processing noise at S, also distributed normally as . Since fraction of received power is used for energy harvesting, thus the amount of harvested energy at S, ignoring small amount of energy stored by antenna and signal processing noise, can be written as [3]where represents the power conversion efficiency at S. The AP transmission is also picked up by the eavesdroppers; the signal received at the information decoder of the th eavesdropper is written aswhere represents the channel gain estimated by the th eavesdropper. Furthermore, represents the thermal noise distributed as and is the signal processing noise identically distributed as at the th eavesdropper. Here the noise statistics are assumed identical due to all eavesdroppers using the same type of hardware. For a tractable analysis, we consider and . Similar to (3), the amount of harvested energy at the th eavesdropper can be written as [3]where is the power conversion efficiency at the th eavesdropper. Moreover, without loss of generality, we consider throughout this work. Finally, the receiver nodes make an erroneous channel estimate due to their hardware impairments modeled as [35, 36]where ; represents the true channel amplitude gain. The parameter is a measure of estimation accuracy with for a perfect estimate. Additionally, is a normal random variable distributed as . Now by substituting (6) into (2) we can express the signal received at S asand substituting (6) into (4) we can express the signal received at th eavesdropper asUsing the above equations, the instantaneous signal-to-noise ratio (SNR) of the main channel can be written asand the SNR for the th wiretap channel can be expressed aswhere and . For subsequent analysis, is considered.

3. Secrecy Outage Analysis

In this section closed-form expressions for the secrecy outage probability are derived separately for four different cases that are based on the receiver types used at S and . Specifically, denotes outage probability for the case of separated receiver architectures at S and , denotes the outage for separated receiver at S and integrated receiver at , is the outage for integrated receiver at S and separated receiver at , and denotes outage probability for the case of integrated receivers at both S and . Each of these four cases is discussed first for the noncooperative eavesdropping scenario and later for cooperation among the eavesdroppers.

3.1. Noncooperative Eavesdroppers

In this scenario, the worst-case of the eavesdropper with the maximum SNR is considered to decode the message. The instantaneous SNR of the wiretap link can be rewritten asHere is Gamma distributed [37] with probability density function (PDF) . Then, the cumulative distribution function (CDF) for the instantaneous SNR of the wiretap link (i.e., random variable falling below an arbitrary value ) is given asNow using statistical independence of the wiretap channels and the CDF of a Gamma random variable [38], we obtain

The corresponding PDF can be written aswhere represents the average SNR of the wiretap link and is the Nakagami-m fading severity parameter for the wiretap link.

The PDF of the instantaneous SNR of the main link can be obtained as [37]The corresponding CDF is given as [37]where is the average SNR of the main link and represents the Nakagami-m fading severity parameter for the main link.

3.1.1. Separated Receivers at and

The achievable rates for the main and wiretap links can be written as and , respectively [3]. The achievable secrecy rate is defined as the nonnegative difference between the achievable rates of the main channel and wiretap channel, which is expressed as . A secrecy outage event occurs when falls below some target rate [39, 40]. The secrecy outage probability is then written asNow using (14) and (15) in (17) and with the help of [41, (8.352.4)], we obtainwhereFurthermore, is the upper incomplete Gamma function and is the Gamma function [41]. The function can be readily evaluated using any computational software.

3.1.2. Separated Receiver at and Integrated Receiver at

In this case the achievable rate for the main link is . On the wiretap link, the integrated receiver’s ID channel can be modeled as a free-space optical intensity channel [3]. The asymptotic high-SNR achievable rate for this channel is expressed as , assuming that the signal processing noise dominates the antenna noise [3, 42]. Then using the approach of (17), we obtainwhere . Substituting (14) and (15) in (20) and using [41, (8.352.4)], we getwhere .

3.1.3. Integrated Receiver at and Separated Receiver at

In this case, the main link has an asymptotic achievable rate of [3, 42], whereas the achievable rate for the wiretapper is . Then using a similar approach to (17) and after some manipulations, the outage probability is given asSubstituting (13) and (15) in (22) and using the binomial theorem, we getwhere involves a single integral and can be readily evaluated in any computational software. Furthermore, and .

3.1.4. Integrated Receivers at and

In this case the main and wiretap links have asymptotic achievable rates of and , respectively [3]. Then using the same approach as that for deriving (17), we obtainReplacing (13) and (15) in (24) and after some algebraic manipulations, we obtainwhere .

3.2. Cooperative Eavesdroppers

For the case of cooperative eavesdropping, the eavesdroppers share information to form a virtual antenna array for received beamforming such that a single-input multiple-output (SIMO) channel exists between the AP and the eavesdroppers [19]. The combined message ensures the maximum achievable rate of the wiretap link. In this case the instantaneous SNR of the combined wiretap signal can be written asThe PDF of can be written as [43]The CDF of the sum of independent, identically distributed Gamma random variables is expressed as [38]

3.2.1. Separated Receivers at and

Using (27) and (15) in (17) and with the help of [41, (8.352.4)], the secrecy outage probability for this case is expressed aswhere .

3.2.2. Separated Receiver at and Integrated Receiver at

Substituting (27) and (15) into (20), the secrecy outage probability for this case is expressed asAfter some simplifications and using [41, (8.352.4)], the secrecy outage probability is expressed as

3.2.3. Integrated Receiver at and Separated Receiver at

Substituting (28) and (15) in (22), the secrecy outage probability for this case is expressed asAfter some algebraic manipulations, we obtainwhere .

3.2.4. Integrated Receivers at and

Replacing (28) and (15) in (24) and using a similar approach for the derivation of 32, the secrecy outage probability for this case is expressed as

4. Numerical Results and Discussion

We now provide some numerical results to validate the analytical expressions derived in Section 3. The system simulation parameters provided in Table 1 are used for result generation, unless stated otherwise.

Figure 3 compares the secrecy performance for different combinations of receiver architectures at the legitimate receiver and the eavesdroppers. Figure 3(a) shows that for any given value of the smallest secrecy outage probability is achieved when S is equipped with a separated and with an integrated receiver architecture. On the other hand, the secrecy outage probability is the largest for the case when S is equipped with an integrated and with a separated architecture, all other parameters remaining unchanged. The figure also shows that the outage probability increases with cooperation between the eavesdroppers. Figure 3(a) shows that by increasing a steady reduction in the outage probability can be achieved. However, at large values ( dB), an outage floor is introduced for both the cooperative and noncooperative cases, which shows that the outage probability does not decrease despite an increase in the main link SNR. This floor appears because of the channel estimation errors for the main link. By comparing Figures 3(a) and 3(b), it can be observed that by increasing the target rate , for a fixed , the outage probability increases for all receiver architecture combinations. Finally, comparing the two subfigures also reveals that the difference between the outage performance with and without eavesdropper cooperation diminishes as is increased from 1 to 2 bps/Hz. All graphs shown in the figures exhibit a good match between the simulation and analytical results, which validates the accuracy of our derived analytical expressions.

(a)

(b)

Figure 4 shows the secrecy outage probability surface plotted against and the Nakagami- parameter, for different receiver architectures at S and . Figure 4(a), for the case of noncooperative eavesdroppers, shows that the secrecy outage probability decreases with an increase in , which corresponds to a decreasing severity of the channel fading. Moreover, the figure shows that progressively larger values of the Nakagami parameter, , result in an increasing difference between the secrecy outage probabilities achieved by the 4 receiver combinations; the combination of S separated and integrated receivers has the smallest outage as already observed in Figure 3. By comparing Figure 4(b), i.e., cooperative eavesdroppers with Figure 4(a) for the noncooperating case, it can be observed that for a given and identical system parameters cooperation between the eavesdroppers significantly increases the secrecy outage probability relative to that for the noncooperative case.

(a)

(b)

Figure 5 shows the impact of the PS factor on the secrecy outage probability. To separately demonstrate the effect of PS at S only, is varied while the PS factor at the eavesdroppers is fixed at . Another set of curves shown in Figure 5 describe the effect of PS at eavesdroppers only, while is maintained for those curves. The figure shows that by increasing values of the secrecy outage probability decreases. This is because a larger fraction of the received power is then used for ID at S. In contrast, the secrecy outage probability increases with increasing values of . This is due to the fact that more power is then allocated by the eavesdroppers to decode the secret message, which diminishes the system’s secrecy performance.

Figure 6 shows the impact of the channel estimation errors on the secrecy outage probability. Figures 6(a) and 6(b) show that an increase in , the legitimate receiver’s estimation error, degrades the secrecy performance. However, Figures 6(c) and 6(d) show that an increase in , the eavesdropping receiver’s estimation error, reduces the secrecy outage probability. This follows from the fact that the secrecy outage event is dependent on the decoding ability of both the legitimate and the eavesdropper nodes. An imperfect channel estimate at the eavesdropper increases its likelihood of incorrect decoding of the secret message, which reduces the information leakage. One may also observe from the figure that an increasing error in CSI estimate of the higher SNR main link has a more dominant effect on the secrecy outage probability than a similar increase in CSI error on the wiretapping receivers. This can be verified by comparing the relative shift in the secrecy outage curves between Figures 6(a) and 6(b) with the relative shift in the secrecy outage between Figures 6(c) and 6(d). This effect is more pronounced for the cooperating eavesdroppers case.

(a)

(b)

(c)

(d)

Figure 7 shows the energy-secrecy capacity tradeoff for both cooperative and noncooperative eavesdroppers. Each tradeoff curve is generated by varying between 0.01 and 0.99 with fixed . However, plotting of each curve in Figure 7 is restricted to its respective subinterval that produces a nonnegative secrecy capacity. This results in different energy levels, harvested according to (), at zero secrecy capacity as shown in Figure 7. One may observe from the figure that the enhanced eavesdropper performance due to cooperation diminishes the harvested energy conditional on a nonnegative secrecy capacity. The figure also shows that achieves a better energy-secrecy operating point than that of , which highlights the significance of having an accurate CSI estimate at the main receiver. Moreover, the figure shows that when the number of eavesdroppers increases from 5 to 10, the area of the energy-secrecy capacity region decreases significantly for both the cooperative and the noncooperative eavesdroppers. Finally, for a fixed number of eavesdroppers, the energy-secrecy capacity region for noncooperative eavesdroppers is larger than that of the cooperative eavesdroppers. This highlights the fact that cooperation among the eavesdroppers considerably degrades the secrecy performance of the system.

5. Conclusion

This work has investigated the secrecy outage probability for a SWIPT system operating in the presence of cooperative eavesdroppers and different combinations of the SWIPT receiver architectures considered at the legitimate receiver and the eavesdroppers. We derived closed-form expressions for the secrecy outage probability for each of these cases and showed that the smallest secrecy outage probability is achieved when the legitimate receiver has a separated architecture and the eavesdroppers have an integrated SWIPT receiver. The worst-case scenario is when the legitimate receiver has an integrated architecture and the eavesdroppers have separated SWIPT architectures; for a high main link SNR and Nakagami-, it was shown that the secrecy outage probabilities achieved for these two extreme cases differ by an order of magnitude. The effect of channel estimation errors was also investigated and it was shown that for the main link average SNR greater than 28 dB, an outage floor appears; i.e., the secrecy outage probability cannot be reduced further due to the channel estimation errors, despite an increase in the main link SNR. Finally, it was shown that cooperation between the eavesdroppers significantly increases the secrecy outage probability relative to that of the noncooperative case for any combination of receiver architectures. Our results are useful for analyzing the secrecy performance of different SWIPT receiver architectures and eavesdropper cooperation.

Conflicts of Interest

The authors declare that they have no conflicts of interest.

Acknowledgments

This work is supported by the EU-Funded Project ATOM-690750, approved under Call H2020-MSCA-RISE-2015.

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Copyright © 2018 Furqan Jameel et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

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