Computer Modeling and Simulation of Ultrasonic Signal Processing and Measurements

Abstract

The system for simulation, measurement, and processing in Graphical User Interface implementation is presented. The received signal from the simulation is compared to that of an actual measurement in the time domain. The comparison of simulated, experimental data clearly shows that acoustic wave propagation can be modeled. The feasibility has been demonstrated in an ultrasound transducer setup for material property investigations. The results of simulation are compared to experimental measurements. The simulation result has good agreement with the experimental data which confirms the validity of the model. The simulation tool therefore provides a way to predict the received signal before anything is built. Furthermore, the use of an ultrasonic simulation package allows for the development of the associated electronics to amplify and process the received ultrasonic signals. Such a virtual design and testing procedure not only can save us time and money, but also can provide better understanding on design failures and allow us to modify designs more efficiently and economically.

1. Introduction

Numerical simulations—that is, the use of computers to solve problems by simulating theoretical models—is part of new technology that has taken place alongside pure theory and experiment during the last few decades. Numerical simulations permit one to solve problems that may be inaccessible to direct experimental study or too complex for theoretical analysis. Computer simulations can bridge the gap between analysis and experiment. Numerical simulations analysis and experiment cover mutual weakness of both experiment and theory. These simulations will remain a third dimension in ultrasonic measurements, of equal status and importance to experiment and analysis. It has taken a permanent place in all aspects of ultrasonic measurements from basic research to engineering design. The computer experiment is a new and potentially powerful tool. By combining conventional theory, experiment, and computer simulation, one can discover new and unsolved aspects of natural process. These aspects could often neither have been understood nor revealed by analysis or experiments alone.

There might be many use of ultrasound but a common one is its application to nondestructive evaluation. Pulsed ultrasonic is finding an increasing number of applications in research and industrial nondestructive testing. In such evaluation, one tries to obtain information about the inner parts of an ensemble without dismantling it. In an ultrasonic system, a transducer consists of a collection of material layers. The design and optimization of a multilayered transducer is a complicated engineering task that involves knowledge of physical acoustics, analog electronics, and the acoustical properties of the materials involved. This task is made even more difficult by the lack of available information about frequency and thermal dependencies of these materials characteristics. The optimal combination of suitable materials can be found by trial and error, but not without considerable time and cost, both of which can be minimized through the use of simulations. The aim of this paper is to present a tool which provides a simulation of the received signal prior to construction. Of the different ways to model the electroacoustic system, a total electrical simulation tool is used for the following reasons. First, the modeling of acoustic wave propagation in one dimension by electrical lines can be handled with a certain ease; second the associated electronics used to excite, receive, amplify, and process the signals can be designed to meet the application’s specifications prior to building system. This paper presents a simulation solution to ease the selection process. The electronic software simulation package used is PSPICE [1]. The use of PSPICE provides an opportunity to simulate the complex set of excitation electronics, the ultrasonic transducer, the material under investigation, and the receiving electronics. Electrical analogies of one-dimensional acoustic phenomenon have studied over the years. Mason [2] modeled electromechanical transducers with a lumped equivalent circuit. Redwood [3] incorporated a transmission line into Mason’s model to obtain useful information about the transient response of a piezoelectric transducer. With the transmission line, one can represent the time delay necessary for a mechanical signal to travel from one side of the transducer to the other. In the case of a plate transducer, the derivation of both models includes a negative capacitor. Using SPICE and an equivalent circuit approximating the negative capacitor, Morris and Hutchens [4] simulated Redwood’s implementation of Mason’s model. Krimholtz et al. [5] presented another equivalent circuit for elementary piezoelectric transducer. Leach [6] used controlled current and voltage sources instead of transformers. Leach mathematically derives his model by adding terms equal to zero in one of the devices electromechanical equations to obtain the form of the telegraphist’s equation. Püttmer et al. [7] used a lossy transmission line in Leach’s model to account for acoustical attenuation. Benny et al. [8] outline a method that has been implemented to predict and measure the acoustic radiation generated by ultrasonic transducers operating into air in continuous wave mode. A comparison of experimental and simulated results for piezoelectric composite, piezoelectric polymer, and electrostatic transducers is then presented to demonstrate some quite different airborne ultrasonic beam-profile characteristics. San Emeterio et al. [9] present an approximate frequency domain electro-acoustic model for pulsed piezoelectric ultrasonic transmitters which, by integrating partial models of the different stages, allows the computation of the emission transfer function and output force temporal waveform. Hirsekorn et al. [10] perform numerical simulations of acoustic wave propagation through sonic crystals consisting of local resonators using the local interaction simulation approach (LISA). The current work applies the approach of Püttmer et al. [7] to liquids and piezoelectric transducer to obtain an electrical analogue of one-dimensional, acoustic wave propagation through such materials. In order to keep things at a manageable level, the following simplifications and assumptions are made. The acoustic propagation travels along one direction and consists of planner longitudinal waves, which are normal to the direction of propagation. The amplitudes are small enough to keep things in linear regions of the devices such that the principle of superposition is not violated. From available material data, such as the modulus of elasticity and Poisson’s ratio, the necessary electrical parameters are deduced. Validation of the theory is achieved by comparing experimental data obtained from different liquids at fixed frequency and temperature.

2. Modeling

The piezoelectric phenomena are modeled using controlled voltage and current sources [6] (Figure 1).

Figure 1 

Equivalent circuit for piezoelectric transducer (the Leach model).

Here 𝑙 is the thickness, 𝑓 is the force, 𝑢 is the particle velocity, 𝑣 is the electrical voltage, 𝑖 is the electrical current, ℎ is the piezoelectric constant, and 𝑠 is the Laplace operator.

The equivalent circuit consists of the static capacitance 𝐶₀ (capacitance between the electrodes), a transmission line (representing the mechanical part of the piezoelectric transducer), and two controlled sources for coupling between the electrical and mechanical parts of the circuit. Suppose an ultrasonic pulse travels through a medium with a finite speed 𝑐 (m/s). This pulse can be pictured as a disturbance to which the medium reacts. In the case of longitudinal wave, the disturbance is a compression or rarefaction of matter, which the medium displaces to return to its equilibrium state. The compression and rarefaction within the medium is related to its density 𝜌 (kg/m³), and the restoring force is related to the medium’s bulk modulus 𝑀 (pa) [11]. Their relationship to the speed of sound is𝑀𝑐=𝑣𝜌. (1)

Similarly, in an electrical transmission line an electrical pulse can travel through it. These pulses are received at the other end of the line after a very short but finite time. The pulses travel at a certain velocity. Similar to the acoustic wave, the electrical pulses are concentrations and rarefaction of electrons within the transmission line [12]. A distributed-parameter network with the circuit parameters distributed throughout the line can approximate a lossy transmission line. One line segment with the length Δ𝑥 can be approximated with an electric circuit as in the following (Figure 2).

Figure 2 

Equivalent circuit of an element of a transmission line with a length of Δ𝑥.

This lossy transmission line model is described by four lumped parameters.(i)𝑅 is the resistance in both conductors per unit length in Ω/m,(ii)𝐿 is the inductance in both conductors per unit length in H/m,(iii)𝐺 is the conductance of the dielectric media per unit length in S/m,(iv)𝐶 is the capacitance between the conductors per unit length in F/m,

where 𝑅 and 𝐺 are zero under lossless conditions.

To derive the parameters we begin by using Kirchhoff’s voltage law on the circuit in Figure 1: 𝑣()()()𝑥,𝑡−𝑅⋅Δ𝑥⋅𝑖𝑥,𝑡−𝐿⋅Δ𝑥⋅𝜕𝑖𝑥,𝑡()𝜕𝑡−𝑣𝑥+Δ𝑥,𝑡=0 (2) which can be written as −𝑣(𝑥+Δ𝑥,𝑡)−𝑣(𝑥,𝑡)()()Δ𝑥=𝑅⋅𝑖𝑥,𝑡+𝐿𝜕𝑖𝑥,𝑡𝜕𝑡 (3) and then letting Δ𝑥→0, we get −𝜕𝑣(𝑥,𝑡)()()𝜕𝑥=𝑅⋅𝑖𝑥,𝑡+𝐿𝜕𝑖𝑥,𝑡𝜕𝑡. (4)

Then we have one equation containing 𝑅 and 𝐿. To get another equation relating 𝐺 and 𝐶, we apply Kirchhoff’s current law on the circuit and get 𝑖()()()𝑥,𝑡−𝐺⋅Δ𝑥⋅𝑣𝑥+Δ𝑥,𝑡−𝐶⋅Δ𝑥𝜕𝑣𝑥+Δ𝑥,𝑡()𝜕𝑡−𝑖𝑥+Δ𝑥,𝑡=0 (5) and letting Δ𝑥→0 in this equation also, we get −𝜕𝑖(𝑥,𝑡)()()𝜕𝑥=𝐺⋅𝑣𝑥,𝑡+𝐶𝜕𝑣𝑥,𝑡𝜕𝑡. (6)

The first order partial differential equations, (4) and (6), are called the general transmission line equations. These equations can be simplified if the voltage 𝑣(𝑧,𝑡) and the current 𝑖(𝑧,𝑡) are time-harmonic cosine functions: 𝑣(𝑥,𝑡)=real𝑉(𝑥)𝑒^𝑗𝑤𝑡,𝑖(𝑥,𝑡)=real𝐼(𝑥)𝑒^𝑗𝑤𝑡, (7) where 𝜔 is the angular frequency. Using (7), the general transmission line equations in (4) and (5) can be written as −𝑑𝑉(𝑥)=𝐼(𝑥),−(𝑥)𝑑𝑥𝑅+𝑗𝜔𝐿𝑑𝐼=𝑉(𝑥).𝑑𝑥𝐺+𝑗𝜔𝐶 (8) These equations are called the time-harmonic transmission line equations. Equation (8) can be used to derive the propagation constant and the characteristic impedance of the line. By differentiating (8) with respect to 𝑥, we get 𝑑²𝑉(𝑥)𝑑𝑥²=𝛾²𝑉(𝑥),𝑑²𝐼(𝑥)𝑑𝑥²=𝛾²𝐼(𝑥), (9) where 𝛾 is the propagation constant: 𝛾=𝛼+𝑗𝛽=𝑅+𝑗𝜔𝐿𝐺+𝑗𝜔𝐶. (10) The real part, 𝛼, of the propagation constant is called the attenuation constant in Np/m and the imaginary part, 𝛽, is called the phase constant of the line in rad/m. The general solution to the differential equation (10) is 𝑉(𝑥)=𝐴𝑒^{−(𝛼+𝑗𝛽)𝑥}+𝐵𝑒^{(𝛼+𝑗𝛽)𝑥}. (11) The time dependence into (11) can be obtained by multiplying 𝑒^𝑗𝜔𝑡 to (11):𝑣(𝑥,𝑡)=𝑉(𝑥)𝑒^𝑗𝜔𝑡=𝐴𝑒^−𝛼𝑥𝑒^{𝑗(𝜔𝑡−𝛽𝑥)}+𝐵𝑒^𝛼𝑥𝑒^{𝑗(𝜔𝑡+𝛽𝑥)}. (12) Equation (12) describes two traveling waves; one traveling in the positive 𝑥 direction with an amplitude 𝐴 which decays at a rate 𝛼, while the other with an amplitude 𝐵 travels in the opposite direction with the same rate of decay. The same type of differential equations governs the propagation of an acoustical wave. In the case of harmonic waves, corresponding to (10) and (9), we have the lossy linearized acoustic plane wave equations: 𝜕²𝑝(𝑥,𝑡)𝜕²𝑥+𝑘²_𝑐𝑝()𝜕𝑥,𝑡=0,₂𝑢(𝑥,𝑡)𝜕²𝑥+𝑘²_𝑐𝑢(𝑥,𝑡)=0, (13) where 𝑝(𝑥,𝑡) (Pa) is the pressure and 𝑢(𝑥,𝑡) (m/s) is the particle velocity [11]. Equivalent to 𝛾,𝑘𝑐 is the complex wave number composed of an attenuation constant 𝛼 (Np/m) and a wave number 𝑘 (rad/m). The general solution of the wave equation (15) is 𝑝(𝑥,𝑡)=𝐴𝑒^−𝛼𝑥𝑒^{𝑗(𝜔𝑡−𝑘𝑥)}+𝐵𝑒^𝛼𝑥𝑒^{𝑗(𝜔𝑡+𝑘𝑥)} (14) and is identical to the solutions obtained in transmission line’s represented by (12). Equation (13) has a solution of the same form. The complex wave number 𝑘_𝑐 is given as 𝑘_𝑐=𝜔𝑐11+𝑗𝜔𝜏, (15) where 𝜏 is the relaxation time [11].

Using (14) and (15), we get 𝜔𝛼=𝑐1√21+(𝜔𝜏)²−11+(𝜔𝜏)^21/2,𝜔𝑘=𝑐1√21+(𝜔𝜏)²+11+(𝜔𝜏)^21/2. (16)

In order to unify the two theories, an impedance type analogy is chosen where mechanical force is represented by voltage and current represents particle velocity. The characteristic impedance becomes important at the boundaries because there the continuity conditions have to be satisfied. Pressure and normal particle velocity must be continuous at the boundaries as voltage and current must be continuous at connections. For the lossy transmission line [12], the characteristic impedance 𝑍_el is 𝑍_el=𝑅+𝑗𝜔𝐿𝐺+𝑗𝜔𝐶, (17) and for the lossy acoustic medium [11], the characteristic acoustic impedance 𝑍_𝑎 is 𝑍_𝑎=𝜌𝑐1+𝑗𝜔𝜏, (18) where 𝜌 is the density of the medium.

Expanding (17) and (10), we obtain 𝑍_el≅𝐿𝐶11+𝑅2𝑗𝜔𝐿⋅𝐺𝐶,1𝛾≅2√𝐿𝐶𝑅𝐿+𝐺𝐶+𝑗𝜔√𝐿𝐶. (19) Considering small but nonnegligible losses, where 𝑅≪𝜔𝐿, 𝐺≪𝜔𝐶, and 𝜔𝜏≪1 the second term of (23) is negligible, leaving the characteristic impedance as 𝐿/𝐶, Similarly from (18), the low loss acoustical characteristic impedance can be approximated as 𝜌𝑐. Also, the wave number 𝑘 from (16) become 𝜔/𝑐. To correlate the two characteristic impedances, we choose an impedance type analogy (Figure 1), in which the force (and not pressure) is represented by voltage and the particle velocity is represented by current. The equivalence between the two systems is 𝑍_el≅𝑍_𝑎⋅𝐴, (20) where 𝐴 (m²) is the cross-sectional area of the acoustic beam.

Assisted with the definition of the low loss characteristic impedances equation, the following relationships can be obtained 1𝐿=𝐴𝜌,𝐶=𝐴𝜌𝑐². (21) The real part of (19) is the attenuation constant 1𝛼=2√𝐿𝐶𝑅𝐿+12√𝐿𝐶𝐺𝐶. (22) Draw a parallel with the classical theory of acoustic attenuation 𝛼_classical=𝛼_𝑣+𝛼_tc, (23) where 𝛼_𝑣 is the coefficient of attenuation due to viscous losses, and 𝛼_tc is the coefficient of attenuation due to thermal conduction. From (21) and (22), we can solve for 𝑅 and 𝐺 to model the attenuations such that 𝑅=2𝜌𝑐𝐴𝛼_𝑣 (24)𝐺=2𝛼_tc𝜌𝑐𝐴. (25) Because the material layers used in this paper have a low heat conductance, the loss due to thermal conduction is negligible, and we let the conductance 𝐺=0.

Equations (21) and (24) are the final equations required for simulation purpose.

2.1. Piezoelectric Transducer

An important task when designing ultrasonic transducers and complete transducer system is the simulation of possible configuration prior to construction. Ultrasonic transducer usually consists of a piezoelectric element and nonpiezoelectric layers for encapsulation and acoustic matching. Points of interest are effects of backing materials, matching layers, piezoelectric materials, layer thickness, electrical matching, and coupling on transducer characteristics like bandwidth, time response on different excitation signals, and ring down behavior. As presented in the introduction, different models have been developed over the years to simulate these transducers. Mechanically, a transmission line 𝑇 of length len (m) represents the acoustical layer. The length is selected to achieve the desired center frequency 𝑓 (Hz) of the transducer. With fixed ends, the piezoelectric plate has a fundamental resonant frequency as 𝑐(𝑇)𝑓=2⋅len, (26) where 𝑐(𝑇) is the velocity of sound through it at temperature 𝑇.

Using (21) and the piezoceramic’s density 𝜌, required for transmission line, 𝐿 and 𝐶 values can be calculated. The mechanical factor 𝑄_𝑚 describes the shape of the resonance peak in the frequency domain. The relation between angular frequency 𝜔, inductance 𝐿, and the resistance 𝑅 is given as [7] 𝑄_𝑚(𝑇)=𝜔𝐿𝑅. (27)

In the electrical section, the static capacitance 𝐶₀ is calculated as 𝐶₀(𝑇)=𝜀^𝑠(𝑇)𝐴len, (28) where 𝜀^𝑠 (C²/Nm²) is the permittivity with constant strain [13].

The latter is related to the permittivity with constant stress (free) 𝜀^𝑇 as 𝜀^𝑇(𝑇)𝜀^𝑠(𝑇)=11−𝑘²(𝑇), (29) where 𝑘(𝑇) is the piezoelectric coupling constant.

The mechanical and electrical sections interact with two current controlled sources. From the mechanical side, the deformation itself is not measurable, but the current representing the rate of deformation is the difference between the velocity of each surface normal to the propagation path, represented by the currents 𝑢₁ and 𝑢₂, which is the rate of deformation. This current (𝑢₁−𝑢₂) controls the current source 𝐹₁. It has a gain equal to the product of the transmitting constant ℎ(N/C) and the capacitance 𝐶₀. ℎ is the ratio of the piezoelectric stress constant 𝑒³³(C/m²) in the direction of propagation and the permittivity with zero or constant strain 𝜀^𝑆. In the thickness mode, it is [13] ℎ(𝑇)=𝑒³³(𝑇)𝜀^𝑠(𝑇). (30)

This source’s output is in parallel with the capacitor 𝐶₀. The result is a potential difference across the capacitor that is proportional to the deformation. In the electrical section, the current through the capacitor 𝐶₀ controls the current source 𝐹₂. The gain for this second current source is ℎ. Its output needs to be integrated to obtain the total charge on the electrodes which proportionally deforms the transducer. The integration is performed by the capacitor 𝐶₁. The voltage controlled voltage source 𝐸₁ with unity gain is a one-way isolation for the integrator.

2.2. Liquids

The speed of sound in a liquid is given as 𝑐(𝑇)=𝑘_𝑠(𝑇)𝜌(𝑇), (31) where 𝑘_𝑠 is the adiabatic bulk modulus [14].

Starting with the Navier-Stokes equation, Kinsler et al. [11] derive the following formula for the coefficient of attenuation due to viscosity: 𝛼(𝑇)=2𝜔²3𝜌(𝑇)𝑐³(𝑇)𝜂(𝑇), (32) where 𝜂(𝑇) is the viscosity of liquid. One of the assumptions made in this derivation is that the bulk viscosity is negligible. Parameters that are temperature sensitive, like viscosity, need to be obtained at the desired temperature for single temperature simulation or as a function of temperature for parametric simulation over a temperature range.

3. Experimental Setup

The block diagram of pulser-receiver system is shown in Figure 3. The experimental circuit which is designed by Gandole et al. [20] is used in this set up. The RF pulse generator generates sharp radio frequency pulses of various frequencies in the range 1 MHz to 10 MHz, having pulse width 2 to 60 microseconds. The repetition rate of the pulses is 1 KHz. The radio frequency pulse is fed to the ultrasonic transducer (piezoelectric). The transducer is excited and sends ultrasonic pulse through the sample. The receiver transducer, which is at the other end of the sample, converts the received ultrasonic pulse into an electrical signal (RF pulse). The details of pulser circuit are given in Gandole et al. [20]. This RF pulse is fed to an amplifier consisting of single stage which is assembled by using transistor BF195. The output of single stage amplifier is again amplified with the help of another amplifier using IC CA3028 in cascade mode. The overall characteristics of amplifier are gain = 50 dB; bandwidth = 15 MHz; input impedance = 10.5 kΩ, and low noise. The stability of IC 3028 amplifier is much higher because of small reverse feedback [21]. After the detection of signal through LM 393 (wide band zero cross detector), the detected signal is fed to unity gain buffer, designed using high speed, low power Op-amp AD 826. The characteristics of AD826 are 50 MHz unity gain bandwidth, 350 V/μs slew rate, 70 ns settling time to 0.01%, and 2.0 mV max input offset voltage. This detected signal is then given to reset input of RS flip-flop, while the outputs of IC 74121 of RF pulse generator are used to set the flip-flop. Therefore, a single pulse is obtained at the output, whose width is the time taken by the pulse to travel through the sample. Time meter having accuracy of 0.01 μs measures the width of the pulse. For the measurement of velocity and attenuation, the sender transducer is firmly fixed at one end of the measuring cell, while receiving transducer is fixed to movable scale (Griffin and Tatlock Ltd. London, Make) having least count 0.0001 cm. The system communicates with personal computer (PC) through 12-bit DAS card. For communication, control and set of parameters of ultrasonic system Graphical User Interface (GUI) were created (Figures 5(a)–5(c)). GUI provides general data representation. In GUI it is possible to change almost all of parameters of measured signal and parameters of signal processing. For link-up with system, functions for control drivers in Dynalog system were used. Then parameters for communication with system were set up. In windows (Figure 5), it is possible to select channel number, polarity (unipolar/Bipolar), and range using DAQ configuration frame. “RUN DAQ” frame is used to open the card using “open” command button, close the card using “close” command button. “Start Scan” command button samples the data (voltage level and time) and stores in buffer memory. “Stop Scan” command button stops the sampling process. Measurement and analysis of received ultrasonic signal is achieved by “Measurement and Analysis” frame. The command button “Transient Response” opens the new window, which displays the transient response of the sampled data. Using the cursor point, it is possible to measure the time and pulse height of received signal. This data is stored in database for further analysis.

Figure 3 

Block diagram of experimental setup.

Figure 4 

Probe layout for liquid samples.

(a)

(b)

(c)

Figure 5 

GUI screen of experimental ultrasonic system.

Matched pair of quartz transducers completely sealed (supplied by Electrosonic Industries, New Delhi.) was used for ultrasonic generation and detection. The frequency of measurement was 2 MHz. Diameter of transducer was 25.4 mm. Also the second set of matched pair of transducer PZT-5A (supplied by Panametrics Videoscan V3456) with center frequency 5 MHz was used. Diameter of transducer was 12.5 mm.

The liquid sample was contained in a measurement cell as shown in Figure 3. A glass bottle of suitable size was cut to form a measuring cell. The bottle was fixed with adhesive araldite in an inner space of double-walled chamber which was made up of thick galvanized sheet. Water circulation arrangement was made through thermostat. Dimensions of double-walled chamber are as height of doubled-walled chamber 6.5 inches, outer diameter 5.5 inches, inner diameter 3.25 inches, height of glass bottle 7.5 inches. The double walled chamber was provided with inlet and outlet for constant temperature water circulation. The lower surface of cell (glass bottle) and double-walled chamber were in the same plane. The double-walled chamber was kept on disc to which sender transducer was fixed. Applying silicone grease made the contact of sender transducer and measuring cell. The lower surface of measuring cell acted as acoustic window through which ultrasonic waves could enter in the measuring cell. The clamps were provided between double-walled chamber and disc to avoid movement of doubled-walled chamber and hence of measuring cell during the ultrasonic measurements.

4. Simulation Setup

The analogous circuit setup is described in Figure 6. Simulation code is given below, to describe the circuit.

Figure 6 

Simulation circuit of the experimental setup.

Here static capacitance is (𝐶₀)=𝐶₁=𝐶₄,𝑅₁=𝑅₅,𝐹₁=𝐹₃,𝐹₂=𝐹₄,𝐸₁=𝐸₂.

4.1. The Pulser-Receiver

The pulser circuitry, shown in Figure 6, consists of a pulse generator using pulse source (𝑉2) having 5 V pulsed voltage, 0 sec delay, 1 ns rise and fall time, 2 μs pulse width and 1 ms period. Another source (𝑉3) is sinusoidal source having 0 offset voltage, 5 V peak voltage, 0 sec delay, 5 MHz frequency, 0 damping factor and phase delay followed by TTL7400, 7407, 1 KΩ resistor (𝑅3), 20 V dc supply (𝑉1), and 2nf capacitor (𝐶3). The pulse start at 20 V and decays to 0 V in 2 μs. The output of the capacitor is connected to the electrical part of the transducer and a parallel damping resistor (𝑅4). The receiving and amplifying electronics are not implemented in this schematic.

4.2. The Transducer and Liquid Samples

The matched pair of piezoelectric material PZT-5A, whose material data is obtained from Benny et al. [8], was chosen and given in Table 1. For simplicity, the front wear plate is omitted, and to reduce the ringing of the echoes a backing material is selected with a characteristic acoustic impedance of 15.8 MPas/m. The thickness of the backing layer should be selected such that no echoes return from it. This fact permits us to model the backing layer with a resistor (𝑅2=𝑅6=2 KΩ). Another matched pair of quartz transducers supplied by Electrosonic Industries, New Delhi, was chosen and whose material data is given in Table 1. The data obtained for the lower surface of cell (glass bottle) is given in Table 1. The data in Table 1, for liquid samples was obtained from standard references [15, 16, 18].

Table 1 

Physical properties of materials at 25°C.

5. Graphical User Interface for Simulation Analysis

Figure 7 shows the Graphical User Interface (“UT Measurements”) for easy access to the basic functionality of the modeled ultrasonic system using PSPICEA_D. The results of mixed-signal simulations can then be plotted in the same Probe window with little effort. The newly developed Graphical User Interface heightens the level of clarity, accelerates the speed of navigation, and improves control of information flow enabling end users to take advantage of the systems full potential.

Figure 7 

GUI screen for modeling and simulation of ultrasonic system.

6. Signal Processing

6.1. Time Domain

In this section, the time domain received signal and experimental signal are compared. The simulation signal is shown in Figure 8(a) and the measured signal is shown in Figure 8(b). Figure 8 shows the first 30 μs pulse received by the 5 MHz transducer with an ethanol sample at 25°C.

(a)

(b)

Figure 8 

Complete transient received by 5 MHz transducer at 25°C, in Ethanol.

Figure 9 shows the first 32 μs pulse received by the 5 MHz transducer in methanol at 25°C. Figure 10 shows the first 36 μs pulse received by the 5 MHz transducer in carbon tetra chloride at 25°C. Figure 11 shows the first 30 μs pulse received by the 5 MHz transducer in acetone at 25°C. Figure 12 shows the first 27 μs pulse received by the 5 MHz transducer in benzene at 25°C. Figure 13 shows the first 25 μs pulse received by the 5 MHz transducer with a distilled water sample at 25° C. Table 2 shows the comparison between the literature values and simulation values of ultrasonic velocity and attenuation for the liquid samples. Figures 14(a)–14(e) show the first 50 μs pulse received by the 2 MHz crystal transducer with binary liquid mixtures of methanol and benzene sample at 25°C.

Table 2 

Ultrasonic velocity and attenuation at 25°C for 5 MHz frequency.

(a)

(b)

Figure 9 

Complete transient received by 5 MHz transducer at 25°C, in methanol.

(a)

(b)

Figure 10 

Complete transient received by 5 MHz transducer at 25°C, in carbon tetra chloride.

(a)

(b)

Figure 11 

Complete transient received by 5 MHz transducer at 25°C, in acetone.

(a)

(b)

Figure 12 

Complete transient received by 5 MHz transducer at 25°C, in benzene.

(a)

(b)

Figure 13 

Complete transient received by 5 MHz transducer at 25°C, in distilled water.

(a)

(b)

(c)

(d)

(e)

Figure 14 

(a) Methanol + benzene mole fraction 𝑋1=0.1952. (b) Methanol + benzene mole fraction 𝑋1=0.4834. (c) Methanol + benzene mole fraction 𝑋1=0.6858. (d) Methanol + benzene mole fraction 𝑋1=0.8359. (e) Methanol + benzene mole fraction 𝑋1=0.9516.

Figures 15(a)–15(e) show the first 50 μs pulse received by the 2 MHz crystal transducer with binary liquid mixtures of methanol and benzene sample at 25°C. Tables 3(a)-3(b) show the comparison between the experimental values and simulation values of ultrasonic velocity and attenuation for the binary liquid mixture samples.

Table 3 

(a) Comparison of measured and simulated values of ultrasonic velocities and attenuations in binary liquid mixtures (methanol and benzene) at 25°C. (b) Comparison of measured and simulated values of ultrasonic velocities and attenuations in binary liquid mixtures (methanol and acetone) at 25°C.

(a)

(b)

(c)

(d)

(e)

Figure 15 

(a) Methanol + acetone mole fraction 𝑋1=0.1678. (b) Methanol + acetone mole fraction 𝑋1=0.4375. (c) Methanol + acetone mole fraction 𝑋1=0.6447. (d) Methanol + acetone mole fraction 𝑋1=0.8090. (e) Methanol + acetone mole fraction 𝑋1=0.8090.

7. Conclusion

Analogy between acoustic media and transmission lines is reviewed, and an analogous electrical model of an ultrasonic transducer using controlled sources is discussed. A simulation model of a complete ultrasonic system is presented. The received signal from the simulation is compared to that of an actual measurement in the time domain. The comparison of simulated, experimental data clearly shows that temperature and frequency dependencies of parameters of relevance to acoustic wave propagation can be modeled. The feasibility has been demonstrated in an ultrasound transducer setup for material property investigations. Comparisons were made for attenuation and velocity of sound for ethanol, methanol, carbon tetrachloride, acetone, benzene, and distilled water. For these materials, the agreement is good. The simulation tool therefore provides a way to predict the received signal before anything is built. Furthermore, the use of an ultrasonic simulation package allows for the development of the associated electronics to amplify and process.