Advances in Statistical Channel Modeling for Wireless Communications
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J. Reig, M.T. MartínezInglés, L. Rubio, V.M. RodrigoPeñarrocha, J.M. MolinaGarcíaPardo, "Fading Evaluation in the 60 GHz Band in LineofSight Conditions", International Journal of Antennas and Propagation, vol. 2014, Article ID 984102, 12 pages, 2014. https://doi.org/10.1155/2014/984102
Fading Evaluation in the 60 GHz Band in LineofSight Conditions
Abstract
An exhaustive analysis of the smallscale fading amplitude in the 60 GHz band is addressed for lineofsight conditions (LOS). From a measurement campaign carried out in a laboratory, we have estimated the distribution of the smallscale fading amplitude over a bandwidth of 9 GHz. From the measured data, we have estimated the parameters of the Rayleigh, Rice, Nakagamim, Weibull, and  distributions for the smallscale amplitudes. The test of KolmogorovSmirnov (KS) for each frequency bin is used to evaluate the performance of such statistical distributions. Moreover, the distributions of the main estimated parameters for such distributions are calculated and approximated for lognormal statistics in some cases. The matching of the above distributions to the experimental distribution has also been analyzed for the lower tail of the cumulative distribution function (CDF). These parameters offer information about the narrowband channel behavior that is useful for a better knowledge of the propagation characteristics at 60 GHz.
1. Introduction
There is an increasing interest in using the unlicensed 60 GHz frequency band for commercial applications because of its capability to provide extremely high data rates beyond 5 Gbps over short distances [1–4].
The IEEE 802.15.3c task group (TG3c) has recently published the standard for the millimeterwave (mmW) based alternative physical layer extension for IEEE802.15.3, that is, physical layer (PHY) and media access control layer (MAC) specifications. The IEEE 802.15.3c [5] is a standard in the 60 GHz band for wireless personal area networks (WPAN) devices in the named wireless gigabit ethernet. Simultaneously, the industry has created the consortium wireless gigabit alliance, commonly called WiGig [6], which is devoted to the development and promotion of wireless communications in the 60 GHz band. This band offers the following advantages: (i) huge and readily available spectrum allocation with 7 GHz in both USA and Japan and 9 GHz in Europe, (ii) dense deployment and high frequency reuse, and (iii) reduced size of devices due to the small wavelength [2]. The output power of 60 GHz devices is mainly limited to 10 mW due to regulations. Moreover, the free space losses in the 60 GHz band are considerably higher than those in the microwave band. Thus, the mmW WPAN devices will be designed to operate mainly in shortrange lineofsight (LOS) environments.
Since high data rates available in the IEEE 802.15.3c standard are achieved with multipleinput and multipleoutput (MIMO) techniques [5], it is of paramount importance to characterize adequately the propagation channel in such band.
Several measurement campaigns have been carried out to model adequately the propagation channel at the 60 GHz band [7–15]. In [7], a stochastic channel model has been derived from measurements conducted in office, private house, library, and laboratory environments. The TripleS and Valenzuela (TSV) statistical model has been proposed in [8] for the mmW band from the wellknown Saleh and Valenzuela (SV) model. A modified SV model has been derived in [9] where the deterministic twopath model is extended to a statistical twopath model by introducing random variables for the antenna position and merging with the conventional SV model which is suitable to express nonlineofsight (NLOS) path components. In [10], power delay profiles (PDPs) and power angle profiles (PAPs) have been measured in various indoor and shortrange outdoor environments. These experimental functions have been compared to results provided with image based on ray tracing techniques, by separating the multipath components (MPCs) in angle of arrival (AOA) and time of arrival (TOA). Measurements in a modern office block addressed to characterize the path loss were carried out in [11]. In [12], Smulders has reviewed the statistical description of an extensive number of measurements campaigns and channel modeling published previously.
As a result of some of such works, the TG3c channel modeling subcommittee released a report where a comprehensive channel model is presented based on measurements conducted in several environments [16].
The high speed interface (HSI) mode of the IEEE 802.15.3c standard is designed for devices with lowlatency and bidirectional highspeed data and uses orthogonal frequency domain multiplexing (OFDM) [5]. Since the guard interval in the OFDMHSI mode is higher than the root mean square (rms) delay spread in the majority of indoor environments [7, 10, 11], an accurate characterization of the narrowband channel is required for the 60 GHz frequency band.
Concretely, smallscale fading analyses in the 60 GHz have been addressed in some works to characterize the received amplitude [12–14]. In [13], the smallscale amplitude in LOS measurements conducted in three corridors of an office block with a bandwidth of 1 GHz was modeled as a Rice distribution. Values of mean and standard deviation of the Rice factor have been reported for two antenna types: an openended waveguide (OWG) and lens. The smallscale amplitude has been found to follow a Rayleigh distribution in an urban environment with ranges up to 400 m [14].
In spite of the numerous researches’ efforts, an extensive study of the smallscale fading amplitude in the 60 GHz frequency band remains still open in the technical literature. Furthermore, the performance of MIMO techniques depends strongly on the multipath characteristics of the signal at the receiver device. Therefore, an exhaustive analysis of the fading phenomenon in the 60 GHz band is vital for the deployment of such systems.
In this paper, we will address an extensive study of the fading distribution in the 60 GHz band with LOS conditions from a measurement campaign carried out in a laboratory. The smallscale amplitude of the received signal is modeled as distributions proposed in the literature for modeling the fading amplitude: Rayleigh, Rice, Weibull, Nakagamim, and  distributions. Recently, several distributions have been proposed to model the smallscale fading in LOS condition [17, 18]. Nevertheless, to the best of the authors’ knowledge, no estimators have been derived for the twowave with diffuse power (TWDP) fading distribution proposed in [17]. In [18], the estimators of the  fading distribution are calculated by using the method of moments with the moments of orders 4th and 6th. It is well known that the higher the order of moments used in the method of moments is, the poorest performance of such estimators is. Therefore, we have not analyzed both distributions in this paper. From experimental data, we have obtained the bestfit distribution and the distribution of the parameters inferred for Rayleigh, Rice, Weibull, Nakagamim, and  distributions.
This paper is organized as follows: firstly, the measurement campaign and the measuring setup are exposed in Section 2. In Section 3, the estimators of the distributions used to model the smallscale fading are presented. Next, Section 4 includes the results of the bestfitting distributions. Finally, the conclusions are discussed in Section 5.
2. Measurement Setup
Measurements have been performed in a laboratory of the Universidad Politécnica de Cartagena, Spain. The scenario consists of a room of dimensions approximately 4.5 7 3 m and it is furnished with several closets, desktops, and computers. The walls are made of plasterboard, whereas the floor is made of concrete. Figure 1 shows a top view of the room where measurements have been performed.
The channel sounder is based on the vector network analyzer (VNA) Rhode ZVA67, which has a dynamic range of 110 dB at 60 GHz. A resolution bandwidth of 10 Hz has been used and the band is 57–66 GHz. Both ports have V/1.85 mm female connectors. The antennas used in the measurements have a 5 dBi gain (manufacturer: Qpar 55 to 65 GHz omnidirectional antennas with V/1.85 mm type connector). A scheme of the channel sounder can be found in Figure 2.
The receiving antenna (Rx) is connected to the receiving port of the VNA using a 2 m coaxial cable, while the signal of the transmitting port of the VNA is twice amplified before being connected to the transmitter antenna (Tx), with a total length cable of 6.5 m (4 m + 2 m + 0.5 m). The reference of the two 25 dB amplifiers is HXI HLNA465. The insertion losses of the cable are around 6 dB/m at 66 GHz. The polarization of antennas is vertical. For each combination of the Tx/Rx, we use virtual arrays by means of a linear positioning system moved by a C4 controller, and measurements can be distinguished into two groups.
Tx12 (corresponding to Rx12): in this case, the transmitter is placed in a bidimensional virtual array, uniform rectangular array (URA) 2D positioner, while the receiver uses a unique position.
Tx36 (corresponding to Rx36 each): both the transmitter and the receiver use uniform linear array (ULA).
The ULA are oriented in the axis corresponding to Figure 1. The URA are oriented in the  and axes.
More details can be found in Table 1. The space between positions is 2 mm in both ULA and URA. The measurement process is controlled by a Matlabbased software executed from a laptop, which is connected to the VNA by a local area network (LAN) and to the C4 controller by a RS232 connection.

Each configuration has a bandwidth of 9 GHz and number of equal space frequency points, which are also summarized in Table 1. The transmitted power by the VNA was set to −10 dBm (in order not to saturate the first amplifier), giving a dynamic range of more than 100 dB at 66 GHz; that is, all of the cable attenuation is compensated by the two amplifiers and the measurement is calibrated using the through method. During the measurement process, nobody was in the room, so the channel can thus be considered as stationary. All of the measurement process has been carefully checked by analyzing the frequency response and by measuring the LOS component in the time domain. An analysis of the pathloss, correlation coefficients, and throughput in such scenario is carried out in [19].
3. Estimators of the SmallScale Fading Distribution
In this section, estimators of the most employed distributions for smallscale modeling are described besides both the probability density functions (PDFs) and the cumulative distribution functions (CDFs). The Rayleigh, Rice, Weibull, Nakagamim, and  distributions can adequately characterize different fading conditions.
There are several methods to estimate parameters in distributions. The maximum likelihood estimation (MLE) is superior to the other estimation methods. Nevertheless, the derivation of MLE estimators cannot be straightforward [20]. For instance, a scalar nonlinear equation system is obtained in MLE method for the  distribution without a single solution. The method of moments (MM) provides in many distributions consistent estimators and the estimating equations are simple in many situations [20]. For the  distribution and Nakagamim distributions, we have used the logmoments method, since it offers more superior performance than MM.
Let be the instantaneous received field strength amplitude expressed in V/m. Thus, the received field strength in dBV/m is given by , where
From the measurements records, we assume a sample size of . Thus, correspond to each observation in linear and logarithmic units, respectively. The sample th raw moments of and are defined as respectively. We can calculate the sample th central moments of and as
3.1. Rayleigh Distribution
If both the inphase and quadrature components of the complex baseband received signal follow a Gaussian distribution with 0 mean and standard deviation , then the amplitude of the received signal , is a Rayleigh random variable (RV). This situation frequently occurs in the NLOS case, where the real and imaginary parts of the MPC fulfill these conditions since they are composed of the sum of a large number of waves. Thus, the sum of enough independent RVs provided the fact that no one of the RV dominates very closely to a normal distribution [21]. Nevertheless, the Rayleigh distribution has been extensively used to model the smallscale received amplitude in several environments due to its simplicity.
Assuming that follows a Rayleigh distribution, the PDF of is given by where , denoting expectation.
Likewise, the PDF of can be written as where is given by (1).
The CDF in linear and logarithm units are given by respectively.
Using the MLE method, can be estimated from the samples as
3.2. Rice Distribution
In LOS situations, very often the received signal is composed of random MPCs, whose amplitude is described by the Rayleigh distribution plus a coherent LOS component which has essentially constant power. The power of this component, denoted by , is frequently higher than the total multipath power, symbolized as .
Hence, the PDF of a Rice distribution can be expressed as where is the modified Bessel function of the first kind with order .
The Rice factor, , extensively used in radio propagation is defined as which represents the ratio between power of the coherent LOS component and the power in the other scattered MPCs.
The PDF of is expressed as where is given by (1).
The CDF of and can be written as respectively, where is the Marcum function [23].
In [24], an efficient algorithm to estimate the and parameters of the Rice distribution with the MM has been derived using the sample mean and the sample standard deviation. This recursive algorithm defines the function where
From a starting point of iteration , we recursively evaluate until , where Δ is the required accuracy. From this point, the parameters of the Rice distribution can be calculated as where has been obtained in the th iteration. Note that the minimum theoretical value of is that corresponds to a Rayleigh distribution; that is, . Hence, if , then is fixed to 0, and from (11) the estimated distribution becomes Rayleigh.
3.3. Nakagamim Distribution
In several environments, the Rayleigh and Rice distributions cannot characterize satisfactorily the behavior of the received signal amplitude. For instance, if two paths are of comparable power and are stronger than all the others, the amplitude signal does not fit neither Rice nor Rayleigh distributions.
The Nakagamim distribution [25] assumes that the received signal is a sum of vectors with random magnitude and random phases with less restriction than both the Rice and Rayleigh distributions, thus providing more accuracy in matching experimental data than the use of such distributions [26].
The PDF of the Nakagamim distribution in linear and logarithmic units is given by where is given by (1), , is the gamma function , and is the fading parameter which provides information about the severity of fading, being the variance operator. For , the Nakagamim becomes a Rayleigh distribution. Compound smallscale fading and shadowing amplitudes can be modeled with Nakagamim distributions with . That is why the standard deviation of the logarithmic amplitude distribution exceeds the maximum theoretical value for a smallscale distribution of 5.57 dB which corresponds to the Rayleigh fading distribution (). Note that the smaller fading parameter, , the higher standard deviation of the log distribution. If we assume that the smallscale and shadowing distribution are independent processes, the variance of the log composite distribution is the sum of the variance of the log smallscale and the log shadowing distributions.
We can easily calculate the CDF of the Nakagamim in linear and logarithmic units as where is the lower incomplete gamma function .
In [27, 28], an approximation of the logmoments method for was derived as where and are the second sample raw moment of given by (2) and the second sample central moment of given by (3), respectively.
3.4. Weibull Distribution
The Weibull distribution has been used to model fading amplitudes mainly in indoor environments [29, 30] where the separation of the smallscale and longterm fading is frequently cumbersome and this distribution can fit well the measurements.
The PDF of the Weibull distribution in both linear and logarithmic units is given by where is given by (1) and and Ω are the shape and scale parameters of the Weibull distribution, respectively.
From (24) and (25), we can easily obtain the CDF of the Weibull distribution in both linear and logarithmic units as
The Weibull distribution turns into the Rayleigh distribution for . Composite smallscale and shadowing distributions can be modeled as Weibull distributions with .
Combining the methods of logmoments and moments, we can easily estimate the parameters of the Weibull distribution as [30] where and are the first sample raw moment of given by (2) and the second sample central moment of given by (3), respectively.
3.5.  Distribution
Recently, in [31], Yacoub proposed the use of the  or generalized gamma distribution to model the fading in nonlinear environments where the surfaces which cause diffuse scattering are correlated spatially. Nevertheless, this distribution had been employed previously in [32] to characterize shadowed channels, that is, composed longterm and smallscale fading effects. The main advantage of the  distribution is its mathematical simplicity and versatility even though it includes important distributions as gamma, Nakagamim, oneside Gaussian, and Rayleigh as particular cases.
The PDF of the  distribution in linear units can be written as where is a parameter which controls the linearity, , and . For , the  distribution becomes a Nakagamim distribution. If and , the  distribution turns into a Rayleigh distribution. For , the  distribution converts into a Weibull distribution.
From (29), the PDF of is obtained as where is given by (1).
We can calculate the CDF of and as
In [33], an estimation of such parameters has been derived based on the logmoments method as where is the polygamma function of first order , and and are the sample central moments of second and third order of , calculated as (5).
4. Results
In this section, we present results of the fading amplitude distributions for the six measurements shown in Table 1 with positions depicted in Figure 1. Firstly, the main parameters of each measurement such as the coherence bandwidth, rms delay spread, and mean delay are calculated. Next, the statistical KolmogorovSmirnov (KS) test is used to evaluate the goodnessoffit of the above distributions, and finally we obtain the distribution of the most important estimators for such distributions. Finally, we have analyzed the matching of the estimated distributions in their lower tails to the experimental distribution.
4.1. Main Wideband Parameters
The principal wideband parameters for each measurement have been included in Table 2. Both mean excess delay and rms delay spread have been calculated from the measured power delay profile (PDP). To mitigate the noise effect on the rms derivation, we have considered a threshold level of 10 dB above the noise level floor. Since the rms delay spreads calculated for all the measurements are considerably smaller than 24.24 ns, which is the guard interval in the OFDMHSI mode [5], the behavior of the PDP profile does not affect substantially the performance of this mode; that is, the intersymbol interference (ISI) is negligible.

The coherence bandwidth has been calculated for a high normalized frequency autocorrelation function value of 0.9; that is, . The coherence bandwidths for all measurements are larger than the subcarrier spacing of 5.15625 MHz in the OFDMHSI mode [5] except for the measurement #4, which is around 5 MHz. Therefore, we can also ignore the time dispersion effect on the system performance.
4.2. BestFit Distribution and KolmogorovSmirnov Test
Using the estimators detailed in Section 3, we have evaluated the inferred Rayleigh, Rice, Nakagamim, Weibull, and  distributions for each point of frequency in each measurement. These distributions are compared to the experimental distributions. To estimate the parameters of the Rice distribution, the accuracy parameter is fixed to 10^{−8}.
In Figure 3, the PDFs of the above distributions in logarithmic units given by (7), (13), (25), (27), and (30) are plotted beside the experimental logarithmic PDF for the 2nd bin (frequency of 57.002 GHz) of the measurement #1. Note that the relationship between the received power in dBm, , and the field strength in dBV/m, , is given by where is the wavelength and is the receiver antenna gain in dB.
The , Weibull, and Rice distributions match rather well the experimental distribution. In fact, the bestfit is the Weibull distribution in this case.
The statistical KS test has been assessed for these distributions over all the bins of frequency in each measurement. The KS confidence interval used is 5%. Moreover, we have calculated the bestfit distribution using the KS test in each measurement. The bestfit distribution is calculated from the minimum value of where is the experimental logarithmic CDF and is the inferred logarithmic Rayleigh, Rice, Nakagamim, Weibull, and  CDFs given by (9), (15), (22), (27), and (32), both of them evaluated in .
Table 3 shows the percentage of the bestfist for the above distributions besides the KS test accomplishment percentage over all the frequency bins in each measurement.

Note that the sum of the bestfit percentages for each measurement is 100%. In bold letters, we have highlighted the maximum bestfit distribution of each measurement. Since the measurements have been carried out in LOS condition, and in accordance with [13, 14], the Rice distribution is the most frequently bestfit distribution in the measurements from #1 to #5. In measurement #6, the Nakagamim is the most frequently bestfit distribution even though the KS test success of 90.5% for this distribution is less than the value of the percentage for the Rice distribution of 94.7%. Furthermore, the KS test for the Rice distribution is fulfilled in at least 84.4% of frequency bins in the worst case, corresponding to the measurement #2. In measurements #3–#5, the KS test percentage for the Rice distribution is very close to 100%.
4.3. Distribution of Estimated Parameters
Once the parameters of the Rayleigh, Rice, Nakagamim, Weibull, and  distributions are estimated from (10), (16)–(19), (23), (28), and (34)–(36), we can obtain the distribution of the main parameters of these distributions for each measurement.
Let and be the skewness and kurtosis of the distribution of the parameter defined as respectively, where is the th central moment of the distribution of . The skewness is a measure of the asymmetry of the PDF of a realvalued RV whereas the kurtosis is an estimation of the “peakedness" of the PDF. A null skewness corresponds to a symmetrical PDF. A lefttailed PDF provides negative skewness and a positive skewness is obtained for righttailed PDFs. Note that the skewness and kurtosis of a Gaussian distribution are equal to 0 and 3, respectively. We can also define the sample skewness, , and sample kurtosis, , of the distribution of in the same way of (2)–(5).
We have observed that the PDF of all the estimated parameters is highly rightskewed. That fact suggests that a lognormal distribution could approximate the distribution of some of these parameters. Therefore, we can evaluate the skewness and kurtosis of the distribution parameters expressed in dB.
Table 4 shows the sample log skewness, log kurtosis, sample mean, and sample standard deviation of the main estimated parameters of the Rice, Nakagamim, Weibull, and  distributions.

Following these results, both the fading parameter, m, of the Nakagamim distribution and the shape parameter, , of the Weibull distribution can be clearly modeled as a lognormal distribution. The Rice factor in dB could also fit a Gaussian distribution in measurements #3, #5, and #6. Nevertheless, both and parameters of the  distribution cannot be modeled as a lognormal distribution in spite of the PDF symmetry due to the small sample skewness values. Figure 4 shows the PDF of the Rice factor in dB and the Gaussian approximation for the measurements #1 and #5. Since the skewness of both factor distributions are very close to 0, the experimental PDFs are symmetrical. In spite of the fact that the kurtosis of the factor distribution, which is equal to 4 in the measurement #1, is slightly different from the theoretical value for the Gaussian distribution that is 3, the appearance of experimental and estimated PDFs is similar.
The mean of the Rice parameter oscillates from 3.21 to 8.45 dB. The values of the Rice parameter mean are equal to or higher than 4 dB except for the measurement #4. Note that the separation between Tx and Rx in the measurement #4 is the highest of all the experiments and the scatterers are closer to the Rx than the rest of the measurements.
The mean of the Rice factor can be related to the mean of the fading parameter, , of the Nakagamim distribution following the method of moments as follows [35]: From (40), the smaller Rice parameter is, the lower fading parameter, , is for . Mean fading parameters vary from 1.54 to 3.87. The standard deviation of the fading parameter is low with a maximum value of 2.06 for the measurement #2. We can compare , defined as the sample mean of the estimated fading parameter with the logmoments method (see Table 4), to , calculated from the sample mean of the estimated Rice factors using (40). Table 5 shows both parameters and the mean of the estimated Rice parameter in both linear and logarithmic units.

From Table 5, it can be observed that and values are similar with a maximum difference between them of 0.4 for the measurement #6.
Figure 5 shows the PDF of the fading parameter in dB, , and the Gaussian approximation for the measurements #2 and #5. In spite of the fact that the kurtosis value of for the measurement #2 is not so different from 3, the difference between the experimental and the Gaussian PDFs is not negligible due to the significant value of skewness of 0.46 which provides a righttailed or rightskewed experimental PDF. Similar conclusion can be extracted for the fading parameter distribution of the measurement #5.
The mean of the shape parameter, , of the Weibull distribution oscillates from 2.7 to 4.71. On the one hand, the distribution is very different from the Rayleigh distribution since the mean of is substantially higher than 2. On the other hand, the longterm fading is negligible in our measurements, since the standard deviation of the distribution in logarithmic units is considerably smaller than 5.57 dB which is the value for the log Rayleigh distribution (). The higher value of the Weibull distribution is, the smaller standard deviation of the logarithmic Weibull distribution is. A composite smallscale and logterm fading logarithmic distribution usually reaches a standard deviation that exceeds 5.57 dB which corresponds to estimated values of the Weibull distribution lower than 2. The standard deviation of the parameter of the Weibull distribution is low varying from 0.51 to 1.2. For the  distribution, we have obtained considerably high standard deviations of the estimated parameter. Therefore, the stability of this estimated parameter is substantially small. Nevertheless, the variation of the mean of the estimated parameter for the  distribution is not considerable since it oscillates from 4.31 to 5.58.
4.4. Lower Tail of the Distributions
In the analysis of performance in wireless communication systems, the lower tail of the distribution influences substantially the parameters, such as the outage probability, the bit error rate (BER), and the symbol error rate (SER), for high average signaltointerference ratios. That is why the matching of the analytical distributions considered in this paper to the experimental distribution in the lower tails has been deeply analyzed in this subsection.
We have defined a relative received power, , for a given value of the experimental CDF, , which can be written as
The relative received power for the Rayleigh, Rice, Nakagamim, Weibull, or  estimated CDFs, , for the same value of the CDF, , is given by Let be the difference between the relative received power of the estimated CDF and the relative received power of the experimental CDF for the same value of the CDF, , defined as In Figure 6, is shown for the Rayleigh distribution in the measurement #6 and the 2nd bin of frequency (57.00488 GHz).
Since the number of samples of each observation is not high, we cannot calculate for low values of , provided that the experimental CDF is not stable for such low values as it can be observed in Figure 6. We can only evaluate this parameter for in the measurements #1 and #6, where the number of samples per record is significantly high.
In Table 6, the mean value and the standard deviation of are calculated for the measurements #1 and #6.

Surprisingly, the bestfit distribution for the low tails is not the same as the bestfit distribution using the KS test for both measurements. In the measurement #1, the bestfit distribution for the low tails is the  instead of the Rice distribution obtained with the KS test. In the same way, the bestfit distribution for the low tails is the Weibull instead of the Nakagamim distribution calculated using the KS test in the measurement #6.
5. Conclusions
In this work, an extensive study of the smallscale amplitude distribution in the 60 GHz band has been carried out for a LOS laboratory environment. Parameters of the Rayleigh, Rice, Nakagamim, Weibull, and  distributions have been estimated and such inferred distributions are compared to the experimental distribution using the KolmogorovSmirnov test. The Rice is the bestfit distribution followed by the  and Nakagamim distributions using the KS test. However, the bestfit distributions for the low tails do not agree to the bestfit distributions obtained using the KS test in the measurements #1 and #6. The KS test for a confidence interval of 5% is fulfilled in over 84.4% of frequency bins for the Rice distribution in the worstcase experiment. From the calculation of the skewness and kurtosis of the logarithmic distribution, we have observed that both the Weibull shape parameter and the Nakagamim fading parameter can be modeled as a lognormal distribution with small standard deviations, with maxima of 1.2 and 2.06, respectively.
Conflict of Interests
The authors declare that there is no conflict of interests regarding the publication of this paper.
Acknowledgments
This work was supported in part by the Spanish Ministerio de Ciencia e Innovación TEC201020841C041 and by the Universitat Politècnica de València, PAID 0511 ref. 2702. The authors thank the anonymous reviewers for their valuable remarks and suggestions which have considerably enriched the final paper.
References
 P. Smulders, “Exploiting the 60 GHz band for local wireless multimedia access: prospects and future directions,” IEEE Communications Magazine, vol. 40, no. 1, pp. 140–147, 2002. View at: Publisher Site  Google Scholar
 C. Park and T. S. Rappaport, “Shortrange wireless communications for nextgeneration networks: UWB 60 GHz millimeterwave wpan, and ZigBee,” IEEE Wireless Communications, vol. 14, no. 4, pp. 70–78, 2007. View at: Publisher Site  Google Scholar
 R. C. Daniels and R. W. Heath Jr., “60 GHz wireless communications: emerging requirements and design recommendations,” IEEE Vehicular Technology Magazine, vol. 2, no. 3, pp. 41–50, 2007. View at: Publisher Site  Google Scholar
 S. K. Yong, P. Xia, and A. ValdesGarcia, 60 GHz Technology for Gbps WLAN and WPAN: From Theory to Practice, Wiley, Chichester, UK, 2011.
 IEEE 802.15.3, Wireless Medium Access Control (MAC) and Physical Layer (PHY) Specifications for High Rate Wireless Personal Area Networks (WPANs) Amendment 2: MillimeterWaveBased Alternative Physical Layer Extension, IEEE, New York, NY, USA, 2009.
 WiGig White Paper: Defining the Future of MultiGigabit Wireless Communication, http:// http://wilocity.com/resources/WiGigWhitepaper_FINAL5.pdf.
 T. Zwick, T. J. Beukema, and H. Nam, “Wideband channel sounder with measurements and model for the 60 GHz indoor radio channel,” IEEE Transactions on Vehicular Technology, vol. 54, no. 4, pp. 1266–1277, 2005. View at: Publisher Site  Google Scholar
 H. Sawada, Y. Shoji, and C. Choi, “Proposal of novel statistic channel model for millimeterwave WPAN,” in Proceedings of the AsiaPacific Microwave Conference (APMC '06), pp. 1855–1858, Yokosuka, Japan, December 2006. View at: Publisher Site  Google Scholar
 Y. Shoji, H. Sawada, C.S. Choi, and H. Ogawa, “A modified SVmodel suitable for lineofsight desktop usage of millimeterwave WPAN systems,” IEEE Transactions on Antennas and Propagation, vol. 57, no. 10, pp. 2940–2948, 2009. View at: Publisher Site  Google Scholar
 H. Xu, V. Kukshya, and T. S. Rappaport, “Spatial and temporal characteristics of 60GHZ indoor channels,” IEEE Journal on Selected Areas in Communications, vol. 20, no. 3, pp. 620–630, 2002. View at: Publisher Site  Google Scholar
 C. R. Anderson and T. S. Rappaport, “Inbuilding wideband partition loss measurements at 2.5 and 60 GHz,” IEEE Transactions on Wireless Communications, vol. 3, no. 3, pp. 922–928, 2004. View at: Publisher Site  Google Scholar
 P. F. M. Smulders, “Statistical characterization of 60GHz indoor radio channels,” IEEE Transactions on Antennas and Propagation, vol. 57, no. 10, pp. 2820–2829, 2009. View at: Publisher Site  Google Scholar
 H. J. Thomas, R. S. Cole, and G. L. Siqueira, “Experimental study of the propagation of 55 GHz millimeter waves in an urban mobile radio environment,” IEEE Transactions on Vehicular Technology, vol. 43, no. 1, pp. 140–146, 1994. View at: Publisher Site  Google Scholar
 M. Choi, G. Grosskopf, and D. Rohde, “Statistical characteristics of 60 GHz wideband indoor propagation channel,” in Proceedings of the IEEE 16th International Symposium on Personal, Indoor and Mobile Radio Communications (PIMRC '05), vol. 1, pp. 599–603, September 2005. View at: Google Scholar
 M. Kyrö, K. Haneda, J. Simola, K. Takizawa, H. Hagiwara, and P. Vainikainen, “Statistical channel models for 60 GHz radio propagation in hospital environments,” IEEE Transactions on Antennas and Propagation, vol. 60, no. 3, pp. 1569–1577, 2012. View at: Publisher Site  Google Scholar
 S. K. Yong et al., “TG3c channel modeling subcommittee final report,” IEEE 802.150758401, 2007. View at: Google Scholar
 G. D. Durgin, T. S. Rappaport, and D. A. De Wolf, “New analytical models and probability density functions for fading in wireless communications,” IEEE Transactions on Communications, vol. 50, no. 6, pp. 1005–1015, 2002. View at: Publisher Site  Google Scholar
 M. D. Yacoub, “The $\kappa $$\mu $ distribution and the $\eta $$\mu $ distribution,” IEEE Antennas and Propagation Magazine, vol. 49, no. 1, pp. 68–81, 2007. View at: Google Scholar
 M.T. MartinezIngles, C. SanchisBorras, J.M. MolinaGarciaPardo, J.V. Rodriguez, and L. JuanLlácer, “Experimental evaluation of an indoor MIMOOFDM system at 60 GHz based on the IEEE802.15.3c standard,” IEEE Antennas and Wireless Propagation Letters, vol. 12, pp. 1562–1565, 2013. View at: Google Scholar
 K. D. Rao, Linear Statistical Inference and Its Applications, John Wiley & Sons, New York, NY, USA, 2nd edition, 1973.
 J. G. Proakis, Digital Communications, McGrawHill, Singapore, 3rd edition, 1995.
 I. S. Gradshteyn and I. M. Ryzhik, Table of Integrals, Series and Products, Academic Press, San Diego, Calif, USA, 7th edition, 2007. View at: MathSciNet
 J. I. Marcum, Table of Q Functions, U.S. Air Force RAND Research Memorandum M339, Rand Corporation, Santa Monica, Calif, USA, 1950.
 C. G. Koay and P. J. Basser, “Analytically exact correction scheme for signal extraction from noisy magnitude MR signals,” Journal of Magnetic Resonance, vol. 179, no. 2, pp. 317–322, 2006. View at: Publisher Site  Google Scholar
 M. Nakagami, “The mdistribution—a general formula of intensity distribution of rapid fading,” in Statistical Methods of Radio Wave Propagation, W. G. Hoffman, Ed., Pergamon Press, Oxford, UK, 1960. View at: Google Scholar
 U. Charash, “Reception through nakagami fading multipath channels with random delays,” IEEE Transactions on Communications, vol. 27, no. 4, pp. 657–670, 1979. View at: Publisher Site  Google Scholar
 R. W. Lorenz, “Theoretical distribution functions of multipath propagation and their parameters for mobile radio communication in quasismooth terrain,” in AGARD Terrain Profiles and Contours in Electromagnetic Wave Propagation, SAO/NASA ADS, 1979. View at: Google Scholar
 J. D. Parsons, The Mobile Radio Propagation Channel, John Wiley & Sons, New York, NY, USA, 2nd edition, 2000.
 H. Hashemi, “Indoor radio propagation channel,” Proceedings of the IEEE, vol. 81, no. 7, pp. 943–968, 1993. View at: Publisher Site  Google Scholar
 R. Ganesh and K. Pahlavan, “On the modeling of fading multipath indoor radio channels,” in Proceedings of the IEEE Global Telecommunications Conference & Exhibition (GLOBECOM '89), vol. 3, pp. 1346–1350, November 1989. View at: Google Scholar
 M. D. Yacoub, “The αμ distribution: a physical fading model for the Stacy distribution,” IEEE Transactions on Vehicular Technology, vol. 56, no. 1, pp. 27–34, 2007. View at: Publisher Site  Google Scholar
 A. J. Coulson, A. G. Williamson, and R. G. Vaughan, “Improved fading distribution for mobile radio,” IEE Proceedings—Communications, vol. 145, pp. 197–202, 1998. View at: Google Scholar
 J. Reig and L. Rubio, “On simple estimators of the αμ fading distribution,” IEEE Transactions on Communications, vol. 59, no. 12, pp. 3254–3258, 2011. View at: Publisher Site  Google Scholar
 M. Abramowitz and I. Stegun, Handbook of Mathematical Functions, National Bureau of Standards, Washington, DC, USA, 10th edition, 1972.
 M. K. Simon and M.S. Alouini, Digital Communications over Fading Channels, John Wiley & Sons, New York, NY, USA, 2nd edition, 2005.
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