International Journal of Antennas and Propagation

Volume 2015, Article ID 358582, 10 pages

http://dx.doi.org/10.1155/2015/358582

## Frequency Diverse Array MIMO Radar Adaptive Beamforming with Range-Dependent Interference Suppression in Target Localization

School of Communication and Information Engineering, University of Electronic Science and Technology of China, Qingshuihexiaoqu, No. 2006 Xiyuan Road, Gaoxin, Xiqu, Chengdu, Sichuan 611731, China

Received 1 February 2015; Accepted 10 September 2015

Academic Editor: Jaume Anguera

Copyright © 2015 Kuandong Gao et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

#### Abstract

Conventional multiple-input and multiple-output (MIMO) radar is a flexible technique which enjoys the advantages of phased-array radar without sacrificing its main advantages. However, due to its range-independent directivity, MIMO radar cannot mitigate nondesirable range-dependent interferences. In this paper, we propose a range-dependent interference suppression approach via frequency diverse array (FDA) MIMO radar, which offers a beamforming-based solution to suppress range-dependent interferences and thus yields much better DOA estimation performance than conventional MIMO radar. More importantly, the interferences located at the same angle but different ranges can be effectively suppressed by the range-dependent beamforming, which cannot be achieved by conventional MIMO radar. The beamforming performance as compared to conventional MIMO radar is examined by analyzing the signal-to-interference-plus-noise ratio (SINR). The Cramér-Rao lower bound (CRLB) is also derived. Numerical results show that the proposed method can efficiently suppress range-dependent interferences and identify range-dependent targets. It is particularly useful in suppressing the undesired strong interferences with equal angle of the desired targets.

#### 1. Introduction

Multiple-input and multiple-output (MIMO) radar has received much attention in recent years. But for conventional colocated MIMO radar, the array manifold caused by time delay only depends on the angle and thus has difficulty in distinguishing the targets and interferences that have the same angle but different ranges by general beamforming techniques [1–3]. Moreover, the localization performance will also be significantly degraded [4, 5] with the targets with the same angle but different ranges. The conventional MIMO radar cannot distinguish range-dependent targets. According to the radar ambiguity function, the range and velocity of a target cannot be simultaneously estimated. Several methods have been suggested to solve these problems. A potential solution is using multiple distributed receivers. But it requires clock synchronization due to separated receivers, which is a technical challenge.

Frequency diverse array (FDA) radar proposed in [6–8] can suppress range-dependent interferences. Different from phased-array radar, a small frequency increment, as compared to the carrier frequency, is applied between FDA elements [9, 10]. This small frequency increment results in a range-angle-dependent beampattern [11–13]. The time and angle periodicity of FDA beampattern was analyzed in [14]. A linear FDA was proposed in [15] for forward-looking radar ground moving target indication. The application of FDA for bistatic radar system was analyzed in [16]. And the imaging of FDA radar was investigated in [17–19]. In [20], we have derived the FDA Cramér-Rao lower bounds (CRLBs) for estimating direction, range, and velocity. Although FDA has drawn much attention in antenna and radar areas, the existing literature concentrates on FDA conceptual system design [21, 22]. Furthermore, most of the FDA MIMO radar literature focuses on beamforming algorithm [23–25], and little work on target localization application and its performance analysis has been reported [26, 27].

In this paper, we design the FDA MIMO radar for range-dependent beamforming and target localization. Our proposed approach exploits jointly the advantages of FDA and MIMO techniques. The advantages of FDA MIMO radar as compared to conventional MIMO radar are investigated. Furthermore, the FDA MIMO radar performance is evaluated by the corresponding transmitting-receiving beampattern, and output signal-to-interference-plus-noise ratio (SINR) is also examined. The contributions of this paper can be summarized as follows. (i) We formulate the data model of FDA MIMO radar. (ii) Range-dependent interferences/targets with the same angle of the targets are suppressed/detected by the FDA MIMO adaptive beamformer. (iii) The CRLB of FDA MIMO radar is derived, along with extensive numerical results. (iv) We derive and verify the resolution probability of FDA MIMO radar localization.

The rest of this paper is organized as follows. In Section 2, we formulate the FDA MIMO radar data model. And we present an FDA MIMO radar adaptive beamforming approach with range-dependent interference suppression in Section 3. In Section 4, the multiple signal classification (MUSIC) algorithm is employed for target localization in angle-range dimension. Simulation results are provided in Section 5. Finally, conclusions are drawn in Section 6.

#### 2. Data Model of FDA MIMO Radar

Consider an FDA MIMO radar equipped with colocated transmitting elements and colocated receiving elements. Assume the transmit and receiving arrays are closely located, so that a target located in far field can be seen by both of them at the same spatial angle. Each transmitting element sends out a distinct omnidirectional waveform , and . Let be the vector collecting all these waveforms. The baseband equivalent model, in complex-valued form, of the transmitted signals from the th transmit element can be expressed aswhereis the th entry of the transmit steering vector with being the frequency increment [25] while is the element space, is the carrier wavelength, denotes the light speed, and and are the target angle and range, respectively. As a comparison, (3) gives the th entry of the steering vector for a phased array, which is not related to the range variable :The FDA MIMO radar transmit steering vector depends on both the range and the angle, whereas that of conventional MIMO radar depends only on the angle. Therefore, the interferences with the same angle of the targets cannot be suppressed by conventional MIMO radar but may be resolved by the FDA MIMO radar.

For a position with angle and range , the phase difference between the two signals transmitted by two adjacent elements isThereby, the transmit steering vector is given byAfter being reflected by the targets or interferences, the signals are received by the colocated receiving array. Taking the first element as a reference, the phase difference of the signals received by two adjacent elements isSimilarly, the receiving steering vector iswhere denotes the transpose operator. The phase difference of the transmit steering vector becomeswhere is caused by reflected range. Therefore, the new transmit steering vector at the receiving array is given bySuppose there is a target located at the position along with multiple interferences located at . receiving complex vector of the receiver observations can be written aswhere stands for the complex amplitude of the target and represents the complex amplitude of the th interference source and is additive zero-mean white Gaussian noise term with covariance matrix , with being the noise power. Note that is the slow time and is the fast time. Since is orthogonal, the received signals can be processed by a matched filter, which outputs an matrix:where and denote the matrix inverse operator and conjugate transpose operator, respectively, and denotes summation operator. Furthermore, it is easy to show that is independent and identically distributed (i.i.d.) Gaussian entries with zero mean and variance . Stacking the columns of , we obtain an virtual data vectorwhere denotes vectorization operator and , anddenotes the joint transmit-receiving virtual steering vector, in which stands for the Kronecker product. The interference-plus-noise covariance matrix can be expressed aswhere denotes the index of interferences and is the averaged power.

#### 3. Adaptive Beamforming and SINR Analysis for FDA MIMO Radar

In this section, we consider the adaptive beamforming which can suppress the range-dependent interferences having the same angle but different ranges from that of targets. The performance is examined in terms of the output signal-to-interference-plus-noise ratio (SINR). For discussion convenience, we rewrite the output of matched filter as follows:To suppress the interferences, the conventional MVDR beamformer for a target located at is employed byThe first term denotes the interference power minimization, and the second term stands for ensuring the target signal without distortion. The weight vector can be solved asHowever, the MVDR beamformer does not make constraints on the sidelobe. In order to suppress the sidelobes, (17) can be reformulated aswhere is the position of the sidelobe and is the sidelobe level. Accordingly, the beampattern is given by

The SINR can be calculated bywhere and are the target signal and interference signals averaged power, respectively, and the diagonal is the noise covariance matrix.

It is well known that inverse of an Hermitian symmetric matrix requires operations. For the FDA MIMO radar, since is an vector, computing and requires and operations, respectively [28]. Then, computation complexity is . The traditional MIMO radar has the same computation complexity. However, traditional MIMO radar has equal transmit and receiving array spacing, and its computing complexity will be [29].

#### 4. FDA MIMO Radar Localization Performance and Resolution Probability Analysis

In this section, we analyze the FDA MIMO radar localization performances in terms of CRLB and resolution probability. The FDA MIMO radar localization can estimate not only target angles, but also target ranges. We can regard both target and interferences as sources. In this case, (13) can be reformulated aswhere the subscript “” denotes the number index of targets. Defining , we can getThe first column is the receiving steering vector given in (9). Thus, we can estimate the target angle through the received signals. Similarly, the range can also be estimated.

According to (22), the covariance matrix can be obtained bywhere is the receiving steering matrix for multiple signals with being the number of targets and . For independent target signals and noise, can be reformulated as where and are the unitary matrices of signal and noise subspaces, respectively, denotes the target signal power, and is the unit matrix. The rank of is equal to the number of targets. Once the number of signals is obtained, the sizes of and are known accordingly. According to the MUSIC principle, the targets can be localized by searching the following peaks:

The eigenvalue decomposition (EVD) of an Hermitian symmetric matrix requires a computation complexity of [28]. According to Section 3, the total computation complexity of an FDA MIMO radar is , which is the same as that of a traditional MIMO radar. When the transmit and receiving arrays have the same element spacing, the computation complexity will be [29].

To derive the CRLB, we rewrite (10) as where with denoting a diagonal matrix. Note that, for notation convenience, has been included in . The unknown parameter vector to be estimated is then given by where , , , and are the real part and image part of , respectively. We divide into deterministic and random components, where are the deterministic parameters and are random components. The Fisher information matrix (FIM) with respect to is where is the noise covariance matrix, denotes the real part, and stands for the trace of a matrix. Equation (31) can be written as where the facts that and are used. Due to the fact that , we can get We take a derivative with respect to where represents the th column of the unit matrix and denotes the derivation of (similar for ). We take also a derivative with respect to , We then have where the fact that is utilized. Define The FIM with respect to part can be calculated by Similarly, we have where and are the real and imaginary part of reflection coefficient , respectively. Defining and , we can get [30] Therefore, the FIM of FDA MIMO radar is derived asFinally, the CRLBs with respect to and are the two diagonal elements of the inverse of the FIM: where is the inverse of and is the element at the th row and th column of the matrix. Since matrices and depend on both range and , the CRLBs are influenced by .

Furthermore, we use the resolution probability defined as follows to compare the localization performance. Two targets can be resolved only when the following relation is achieved: where and are the true directions.

#### 5. Simulation Results

Suppose the following simulation parameters: , GHz, , m/s, KHz, , dB, and . The additive noise is modeled as complex Gaussian zero-mean spatially and temporally white random sequences.

*Example 1 (adaptive beamforming and performance analysis). *In the first example, one target of interest and multiple interferences are located at = (10°, 10 km) and = (10°, 6.5~9 km), respectively.

Figure 1(a) gives the adaptive beampattern of conventional MIMO radar. Obviously, it cannot suppress the interferences having the same angle as the targets shown in Figure 2. In this case, the interferences will degrade the SINR performance. In contrast, the beampattern mainlobe of FDA MIMO radar can be steered to suppress range-dependent interferences, as shown in Figure 1(b) and Figure 2. The FDA MIMO radar beampattern has zero nullings at the interference locations and, thus, the sidelobes are significantly suppressed.