Research Article  Open Access
HuaWei Zhou, XueXia Yang, Sajjad Rahim, "Synthesis of the Sparse UniformAmplitude Concentric Ring Transmitting Array for Optimal Microwave Power Transmission", International Journal of Antennas and Propagation, vol. 2018, Article ID 8075318, 8 pages, 2018. https://doi.org/10.1155/2018/8075318
Synthesis of the Sparse UniformAmplitude Concentric Ring Transmitting Array for Optimal Microwave Power Transmission
Abstract
Beam capture efficiency (BCE) is one key factor of the overall efficiency for a microwave power transmission (MPT) system, while sparsification of a largescale transmitting array has a practical significance. If all elements of the transmitting array are excited uniformly, the fabrication, maintenance, and feed network design would be greatly simplified. This paper describes the synthesis method of the sparse uniformamplitude transmitting array with concentric ring layout using particle swarm optimization (PSO) algorithm while keeping a higher BCE. Based on this method, uniform exciting strategy, reduced number of elements, and a higher BCE are achieved simultaneously for optimal MPT. The numerical results of the sparse uniformamplitude concentric ring arrays (SUACRAs) optimized by the proposed method are compared with those of the randomlocated uniformamplitude array (RLUAA) and the steppedamplitude array (SAA), both being reported in the literatures for the maximum BCE. Compared to the RLUAA, the SUACRA saves 32% elements with a 1.1% higher BCE. While compared to the SAA, the SUACRA saves 29.1% elements with a bit higher BCE. The proposed SUACRAs have higher BCEs, simple array arrangement and feed network, and could be used as the transmitting array for a largescale MPT system.
1. Introduction
Microwave power transmission (MPT) technology transfers power from one location to another by the microwave beam, which could be applied in supplying power to the space power satellites, unmanned aerial vehicles, the farreached areas, and so on [1]. For a largescale MPT system, the most important parameter is the beam capture efficiency (BCE), which is the ratio of the captured microwave power by the receiving antenna array to the transmitted power by the transmitting antenna array [2].
In 1974, Dr. Brown performed an MPT experiment with a distance of 1.7 m in the laboratory. The overall efficiency up to 54% and the BCE is 95% [3]. However, the MPT experiment carried out next year only obtained an overall efficiency of 7% and BCE of 11.3% when the range was 1.54 km [4]. Until now, the overall efficiency of a MPT system is not higher than 10% because of a low BCE [2].
The transmitting aperture illuminated by the Gaussian amplitude distribution can obtain a maximum beam capture efficiency BCE^{max} higher than 99% because of the broad beam width and low side lobe level in the far field [5]. Discrete transmitting aperture, namely, antenna array, is more practical for expanding the MPT system to a large scale. The optimized excitation amplitudes of a planar array for the BCE^{max} can be achieved by solving generalized eigenvalue problem [6]. Nevertheless, owing to the continuous amplitude distribution, many different amplifiers would be required for every distinct element, which results in a complex transmitting array. To reduce the kinds of amplifiers, Baki et al. and Li et al. [7, 8] proposed the isosceles trapezoidal distribution (ITD) and steppedamplitude arrays (SAAs), respectively. The design and implementation of transmitting array could be greatly simplified if all elements are uniformly excited [9]. The randomlocated uniformamplitude array (RLUAA) comprising of 100 elements was optimized by particle swarm optimization (PSO) algorithm with a BCE of 89.96% being obtained [10]. However, the computation amount would grow up rapidly as the element number increases, which could not be applied in a largescale transmitting array design.
Besides the exciting strategy, the sparsification of a largescale transmitting array has a practical significance. Sparse arrays can not only reduce the complexity of the feed networks but also can decrease the weight. Most studies on sparse antenna arrays [11–13] are focused on reducing the number of elements, the peak side lobe level, the computational effort, and so on but not considering the power transmission efficiency. In the MPT scenario, the element numbers of antenna arrays were reduced to 65% and 64% of the original one through compressive sensing (CS) and convex programming (CP) methods, respectively, in [14, 15]. By combining these two methods, the element number was reduced to 54% of the original one and the BCE was improved about 3.16% [16]. Unfortunately, arrays in [14–16] were not uniformly illuminated. Moreover, CS and CP would not be efficient for the largescale array design due to strong nonlinear relationship between the array factor and the element positions [17]. The Besselapproximation array factor of a concentric ring array (CRA) is only related to the radius and excitation of each ring, which would reduce the computation amount and could be used in optimizing a largescale array.
PSO algorithm was firstly introduced by Kennedy and Eberhart in 1995 [18]. Due to its high search efficiency, PSO has been widely used in enhancing antenna gain [19] and beam pattern synthesis [20] and improving BCE of a MPT system [10]. In this work, the synthesis of the sparse uniformamplitude transmitting array is discussed for the optimal MPT. The exciting strategy, element number, and BCE are considered simultaneously for the MPT system. The outline of this paper is organized as follows. Section 2 describes the calculation equations of BCE of the sparse uniformamplitude CRA (SUACRA). Section 3 introduces the optimization model for the SUACRA, and Section 4 presents the numerical results of SUACRAs, which have been compared with those of RLUAA discussed in [10] and SAA proposed in [8].
2. Theoretical Foundation
As shown in Figure 1, the transmitting array is a CRA located in the XOY plane with an element in the center, and the radial space between the (m − 1)th and the mth rings is denoted by . All elements are excited by the identical phase and amplitude.
The receiving array is in the far region of the transmitting array, namely, , where is the distance between transmitting and receiving array, is the radius of transmitting array, and is the wavelength. As a result, the CRA array factor can be written as [21] where is the array factor of mth ring, , , and represent the radius, the element number and the excitation amplitude of the mth ring, respectively, denotes the wavenumber, and is the azimuth angle of the nth element located on the mth ring.
elements are distributed with the same space on the mth ring. When is large enough, array factor of the mth ring can be approximated as [21]
In (4), T_{m} = I_{m}N_{m} and J_{0} is the zeroorder Bessel function of the first kind. To evaluate the precision, the power error index is defined as where is the visible region (0 ≤ θ ≤ π, 0 ≤ φ ≤ 2π) of the transmitting array. Under the constraint of keeping a higher precision of (4), the minimum element number can be found by increasing from 2 till to reach ς_{m} ≤ −30 dB. The line labeled by numerical results in Figure 2 lays out the for radiuses ranging from 0.5λ to 19.5λ with an interval of 0.5λ.
By applying the fitting method, can be approximated to the following formula: where “” stands for mapping number to the least integer that is greater than or equal to the original number. The fitting line is plotted in Figure 2. It can be seen that the fitting results are consistent well with the numerical results. Equation (6) could be used to estimate on a ring of a largescale array.
With the element numbers on each ring not less than the minimum ones, namely, , the CRA array factor of (1) can be rewritten as where , , and superscript “” stands for transpose and complex conjugate. The CRA power pattern is
Therefore, the BCE can be calculated by the following formula: where shows the receiving region, is the received power, and is the total transmitting power. and are all matrixes. The elements of and are calculated as
In the above equations, and . Considering the uniform exciting strategy, namely, for , can be simplified as . is the element number matrix. The BCE of the uniformamplitude transmitting array, denoted by BCE^{U}, can be achieved by
When the is defined, the matrices of and can be calculated from . According to (2), is directly determined by applying the radial space matrix . Therefore, from the given Δρ and N, the BCE^{U} can be calculated by using (11).
3. Optimization Model of SUACRA
Sparsification ratio of a transmitting array is defined as the ratio of the saved element number of the sparse array to that of the original one. In this paper, the radial space matrix and the element number matrix are simultaneously optimized to improve the at the most extent while the BCE^{U} is kept as high as possible. The optimization model can be established as follows: where and are weights of the BCE^{U} and , respectively, and . In order to investigate the impact of BCE^{U} on the , the penalty factor and penalty function have been introduced in (13). The is defined as
BCE_{0} in (15) is the threshold value of BCE^{U}, which is set to be 1% lower than the maximum BCE^{U} of the SUACRA, as denoted by BCE^{Umax}.
From (15), when . In order to maintain , should be large enough, such as 10^{5}, to magnify the impact of the on the fitness function. In this way, could change toward zero in the PSO procedure. Otherwise, should be set to zero to invalidate the .
The radial space Δρ_{m} should not be less than and can be guaranteed by (14), where is the minimum space between the adjacent elements on the planar array. In order to ensure the space along ring path between the adjacent elements larger than , the element number of mth ring should satisfy this condition: where “” stands for mapping number to the greatest integer that is less than or equal to the original number. should not be less than to keep the accuracy of (4), namely, power error index ς_{m} ≤ −30 dB. Moreover, the size of SUACRA is confined by , in which is the expected maximum diameter.
The variable set is , while the fitness function is stated in (13). Each particle of the swarm characterizes a candidate solution, which can be evaluated by the fitness function. After each iteration, the optimal particle is obtained, and each particle is updated. When the termination condition is satisfied, the optimal variable values can be obtained as the optimal particle over the iteration history. For details of the PSO, readers could refer to [20] and the references therein.
4. Numerical Results
The SUACRAs are optimized by the proposed procedure and method. The numerical results will be compared with those of the RLUAA in [10] and the SAA in [8] on the condition of the same transmitting aperture size and the same inception angle.
4.1. Synthesis of the SUACRA Compared with the RLUAA
The RLUAA, the first model optimized in [10], consists of 100 elements distributed arbitrarily on an aperture of 4.5λ × 4.5λ, in which the minimum element distance was 0.4λ and the inception angle was θ_{0} = 0.201. The optimization of the SUACRA is carried out for the same transmitting aperture and the same inception angle, which is denoted by SUACRA 1. In order to further improve the sparsification ratio of , the SUACRA 2 is investigated with a 1% decrease of BCE^{U} compared to that of SUACRA 1. The numerical results are listed in Table 1, and the layouts of SUACRA 1 and 2 are given in Figure 3.

(a)
(b)
In order to improve the sparsification ratio of and keep BCE^{U} as high as possible, in the optimization of SUACRA 1, and are set to 0.99 and 0.01, respectively. Penalty factor is set as 0 to invalidate . As shown in Table 1, SUACRA 1 has a BCE^{U} of 91.06%. Compared to the RLUAA, SUACRA 1 saves 32% elements and has a 1.1% higher BCE^{U}.
With 1% decrease of BCE^{U} of SUACRA 1, the threshold of BCE_{0} is set to 90.06%. In order to improve at the most extent, and are set to 0 and 1, respectively. The penalty factor is set as 10^{5} to guarantee BCE^{U} ≥ BCE_{0}. The numerical results show that the of the SUACRA 2 is improved by 12% with 0.98% decrease of BCE^{U}, which means that the element number is reduced to 56% of the original RLUAA.
As shown by the SUACRAs’ power patterns given in Figure 4, SUACRAs can concentrate microwave power on the receiving region. When θ is close to π/2, the pattern of SUACRA 2 is not symmetrical with respect to the center (θ = 0, φ = 0), because the element numbers of rings is close to the minimum ones. Nevertheless, the difference is just 0.15% between the accurate BCE (90.08% obtained by (1)) and the approximate one (90.23% obtained by (7)). Moreover, the power patterns (φ = 0) comparison of two SUACRAs and the original RLUAA are given in Figure 5. Compared to the RLUAA, the two SUACRAs have lower side lobes and higher main lobe levels. Therefore, the two SUACRAs have higher BCE^{U} of 91.06% and 90.08%, respectively. The side lobe of SUACRA 1 is a little bit lower than that of the SUACRA 2, which results in the difference of 0.98% BCE^{U}.
(a)
(b)
The initial and optimized parameters of SUACRA 1 and 2 are given in Table 2. The initial and are set to and , respectively. Because the diameter of the 6th ring of the initialized array will be larger than the maximum aperture size 4.5λ, parameter is set as 5. The symbol “del” in Table 2 means that the according ring is deleted because the diameter of the ring is larger than 4.5λ. In the optimization, the population size is set as 60. As shown in Figure 6, the fitness values of the two SUACRAs rapidly reach the convergence points within 50 iterations.

4.2. Synthesis of the SUACRA Compared with the SAA
The first discrete aperture example, namely, the SAA, in [8] consists of 316 elements distributed on a circular aperture of diameter , in which the inception angle was 0.107. The optimization of the SUACRA is carried out for the same transmitting aperture and the same inception angle, which is denoted by SUACRA 3. In order to further improve the sparsification ratio of , the SUACRA 4 is investigated with 1% decrease of BCE^{U} compared to that of SUACRA 3. The numerical results are listed in Table 3, and the layouts of SUACRA 3 and 4 are given in Figure 7.

(a)
(b)
Compared to the SAA, SUACRA 3 saves 29.1% elements and has a bit higher BCE^{U}, while the of the SUACRA 4 is improved by 9.8% with 1% decrease of BCE^{U}.
The power patterns of SUACRA 3 and 4 are given in Figure 8, and the special power patterns (φ = 0) comparison of SUACRA 3, 4 and the original SAA are given in Figure 9. It could be seen that the main beams of the three arrays are almost the same although their side lobes are different. SUACRA 3 and the SAA have the same BCE^{U} of 92.5%. The side lobe of SUACRA 4 is a little bit higher than that of SUACRA 3, which results in 1% decrease of BCE^{U}.
(a)
(b)
The initial and optimized parameters of SUACRA 3 and SUACRA 4 are given in Table 4. The parameter is set as 11, and the population size is set as 120. As shown in Figure 10, the fitness values of the two SUACRAs reach the convergence points within 150 iterations.

5. Conclusion
In this paper, the synthesis of the sparse uniformamplitude transmitting array is discussed. As a result, uniform exciting strategy, reduced element number, and a higher BCE are achieved simultaneously for the optimal MPT. Accordingly, the fabrication, maintenance and feed network design of the transmitting array are greatly simplified without loss of BCE. The numerical results show that the SUACRAs optimized by the proposed method have fewer elements than the random array and the stepped one on the same BCE^{U}. Compared to the RLUAA, the SUACRA saves 32% elements with a 1.1% higher BCE^{U}, while the sparsification ratio is improved by 12% with 0.98% decrease of BCE^{U}. Compared to the SAA, the SUACRA can save 29.1% with a bit higher BCE^{U}, and the sparsification ratio is improved by 9.8% with 1% decrease of BCE^{U}. The proposed SUACRAs have higher BCEs, simple array arrangement and feed network, and could be used as the transmitting array for a largescale MPT system.
Data Availability
The data used to support the findings of this study are available from the corresponding author upon request.
Conflicts of Interest
The authors declare that they have no conflicts of interest.
Acknowledgments
This work was supported by Natural Science Foundation of China (Grant no. 61271062 and Grant no. 61771300).
References
 J. O. McSpadden and J. C. Mankins, “Space solar power programs and microwave wireless power transmission technology,” IEEE Microwave Magazine, vol. 3, no. 4, pp. 46–57, 2002. View at: Publisher Site  Google Scholar
 X. X. Yang, “Antennas in microwave wireless power transmission,” Handbook of Antenna Technologies, pp. 1–37, 2014. View at: Google Scholar
 R. M. Dickinson and W. C. Brown, “Radiated microwave power transmission system efficiency measurements,” Tech. Rep., Tech. Rep. 142986, Jet Propulsion Lab, California Institution of Technology, Pasadena, CA, USA, 1975. View at: Google Scholar
 R. M. Dickinson, “Performance of a highpower, 2.388GHz receiving array in wireless power transmission over 1.54 km,” in 1976 IEEEMTTS International Microwave Symposium, pp. 139–141, Cherry Hill, NJ, USA, June 1976. View at: Publisher Site  Google Scholar
 S. Takeshita, “Power transfer efficiency between focused circular antennas with Gaussian illumination in Fresnel region,” IEEE Transactions on Antennas and Propagation, vol. 16, no. 3, pp. 305–309, 1968. View at: Publisher Site  Google Scholar
 G. Oliveri, L. Poli, and A. Massa, “Maximum efficiency beam synthesis of radiating planar arrays for wireless power transmission,” IEEE Transactions on Antennas and Propagation, vol. 61, no. 5, pp. 2490–2499, 2013. View at: Publisher Site  Google Scholar
 A. K. M. Baki, N. Shinohara, H. Matsumoto, K. Hashimoto, and T. Mitani, “Study of isosceles trapezoidal edge tapered phased array antenna for solar power station/satellite,” IEICE Transactions on Communications, vol. E90B, no. 4, pp. 968–977, 2007. View at: Publisher Site  Google Scholar
 X. Li, B. Duan, L. Song, Y. Zhang, and W. Xu, “Study of stepped amplitude distribution taper for microwave power transmission for SSPS,” IEEE Transactions on Antennas and Propagation, vol. 65, no. 10, pp. 5396–5405, 2017. View at: Publisher Site  Google Scholar
 A. Massa, G. Oliveri, F. Viani, and P. Rocca, “Array designs for longdistance wireless power transmission: stateoftheart and innovative solutions,” Proceedings of the IEEE, vol. 101, no. 6, pp. 1464–1481, 2013. View at: Publisher Site  Google Scholar
 X. Li, B. Duan, J. Zhou, L. Song, and Y. Zhang, “Planar array synthesis for optimal microwave power transmission with multiple constraints,” IEEE Antennas and Wireless Propagation Letters, vol. 16, pp. 70–73, 2017. View at: Publisher Site  Google Scholar
 Z. K. Chen, F. G. Yan, X. L. Qiao, and Y. N. Zhao, “Sparse antenna array design for MIMO radar using multiobjective differential evolution,” International Journal of Antennas and Propagation, vol. 2016, Article ID 1747843, 12 pages, 2016. View at: Publisher Site  Google Scholar
 D. Pinchera, M. D. Migliore, F. Schettino, M. Lucido, and G. Panariello, “An effective compressedsensing inspired deterministic algorithm for sparse array synthesis,” IEEE Transactions on Antennas and Propagation, vol. 66, no. 1, pp. 149–159, 2018. View at: Publisher Site  Google Scholar
 X. Zhao, Y. Zhang, and Q. Yang, “Synthesis of sparse concentric ring arrays based on Bessel function,” IET Microwaves, Antennas & Propagation, vol. 11, no. 11, pp. 1651–1660, 2017. View at: Publisher Site  Google Scholar
 P. Rocca, G. Oliveri, and A. Massa, “Innovative array designs for wireless power transmission,” in 2011 IEEE MTTS International Microwave Workshop Series on Innovative Wireless Power Transmission: Technologies, Systems, and Applications, pp. 279–282, Uji, Kyoto, Japan, May 2011. View at: Publisher Site  Google Scholar
 A. F. Morabito, A. R. Laganà, and T. Isernia, “Optimizing power transmission in given target areas in the presence of protection requirements,” IEEE Antennas and Wireless Propagation Letters, vol. 14, pp. 44–47, 2015. View at: Publisher Site  Google Scholar
 A. F. Morabito, “Synthesis of maximumefficiency beam arrays via convex programming and compressive sensing,” IEEE Antennas and Wireless Propagation Letters, vol. 16, pp. 2404–2407, 2017. View at: Publisher Site  Google Scholar
 Q. Guo, C. Chen, and Y. Jiang, “An effective approach for the synthesis of uniform amplitude concentric ring arrays,” IEEE Antennas and Wireless Propagation Letters, vol. 16, pp. 2558–2561, 2017. View at: Publisher Site  Google Scholar
 J. Kennedy and R. Eberhart, “Particle swarm optimization,” in Proceedings of ICNN'95  International Conference on Neural Networks, pp. 1942–1948, Perth, WA, Australia, NovemberDecember 1995. View at: Publisher Site  Google Scholar
 S.I. Kang, K.T. Kim, S.J. Lee, J.P. Kim, K. Choi, and H.C. Kim, “A study on a gainenhanced antenna for energy harvesting using adaptive particle swarm optimization,” Journal of Electrical Engineering and Technology, vol. 10, no. 4, pp. 1780–1785, 2015. View at: Publisher Site  Google Scholar
 C. Han and L. Wang, “Array pattern synthesis using particle swarm optimization with dynamic inertia weight,” International Journal of Antennas and Propagation, vol. 2016, Article ID 1829458, 7 pages, 2016. View at: Publisher Site  Google Scholar
 C. A. Balanis, Antenna Theory: Analysis and Design, Chapter 6, John Wiley & Sons, third edition, 2005.
Copyright
Copyright © 2018 HuaWei Zhou et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.