Research Article | Open Access

# A New Demodulation and Modulation Method Designed for FMCW Radar

**Academic Editor:**John N. Sahalos

#### Abstract

An efficient demodulation method designed for FMCW (Frequency-Modulated Continuous Wave) radar is presented. It is a kind of modified DFT (IDFT) algorithm; the spectrum segment of interest can be easily extracted from the original signal without calculating the whole DFT/FFT. It provides fast demodulation and extraction of desired frequency bands in our HFSWR (High-Frequency Surface Wave Radar) system. The proposed approach enhances the performances of radar system and reduces the computing complexity. The new structure could also be inversely used for signal modulation. And also arbitrary sampling rate conversion could be achieved with the combination of forward and backward structure.

#### 1. Introduction

FMCW is a radar system where a known stable frequency continuous wave radio energy is modulated by a triangular modulation signal so that it varies gradually and then mixes with the signal reflected from a target object with this transmit signal to produce a beat signal. With the advent of modern electronics, the use of Digital Signal Processing is used for most detection processing. The beat signals are passed through an Analog-to-Digital converter, and digital processing is performed on the result [1]. Fast calculating of demodulation and target detecting/tracking is an important issue in radar system design. In order to get higher Signal-to-Noise Ratio, high-speed sampling is used during Analog-Digital Converting. However, high sampling rate brings large bound of data for processing, which reduces performance of the real-time processing. SRC (Sampling Rate Conversion) method is widely used to isolate the desired channel (in frequency domain) in the communication systems [2]. Many different Digital Down-Converter (DDC) structures have been implemented, and the programmable part of decimation structure includes FIR filter, comb filter, and so on. The SRC turns out to be mainly a problem of designing appropriate filters and structures implement [3]. In this paper, combining with the principle of FMCW radar demodulation and the receiver structure, an efficient demodulation structure is proposed, and further extensions are also presented.

#### 2. Signal Processing in FMCW Radar System

Frequency-Modulated Continuous Wave mechanism has been widely used in modern radar system. The waveform parameter of the mechanism is described as follows:

where is radar carrier frequency, is the sweep rate, and is the sweep repetition period; the received signal is a delayed (time ) and scaled (factor ) replica of the transmit signal:

The time delay can be extracted from and , by the demodulation , which is a simple function of the target range and velocity [4, 5]:

where is the initial target range, is the velocity, is the speed of the light, and is the sweep number. Figure 1 gives the sketch of transmit and receive signal of FMCW system.

As shown by Barrick, and others [4, 6, 7], the frequency of the demodulated signal is approximately proportional to target's delay time by

The range of specific targets can be extracted from the frequency of demodulated signal . ADC is used to generate the discrete sequence ; and according to sampling theory, in normal situation, if sampling rate is much higher than the band of desired signal , the higher Signal-to-Noise Ratio can be achieved [2]. In HF radar measurement, the corresponding maximum frequency offset (calculated from the detecting physical limitation) is only several hundred Hz [4]. But the radar system operates in high-frequency band. The noise outside the receiver is dominant other than noise inside the receiver. So an appropriate sampling clock is determined according to outside noise level and the SNR we can get.

#### 3. Principle of the Fast Demodulation in FMCW

As discussed above, the frequency information can be extracted from Fourier Transform (FT) of . may be given by

We define points are sampled in each repetition period. An evaluation of (5) using Fourier transform (FT) would result in points in frequency domain. But according to the maximum offset related to the maximum detecting range (as we have discussed above). Frequency resolution of FT result is [8], from the maximum frequency offset and frequency resolution. The desired frequency points are determined. The first points are enough for target detecting and further signal processing. Normally, is set to ( is positive integer; appropriate is selected also according to -point FFT block in hardware), so we have points, and . If the processor is very powerful and with enough storage memory, surely, it can process the whole sequence with once FFT calculation. But usually, the system needs to process multichannel received signals and some further processing including target detecting and tracking. So the efficiency of the processing must be considered.

The new structure is described as follows: we expand (5)

We get the sum of each column, for example, the sum of th column ():

According to the Fourier transform formula,

From formulas (7), (8), and (9), we will get

If we separate the result of total FT of into segments, we get

where is a value of , the Factor is defined as , and the output is . If we define

Then we can get , which is the th segment of the total FT (as shown in (10)). Figure 2 shows the block diagram of the principle of the proposed structure. is the result of demodulation. So the -point Fourier transform of sequence can be replaced by the sum of a relative shorter -point FFT which will be multiplied by a series of factor . So the analytic frequency band is converted to , which meets the need of the echo signal processing as analyzed in Section 2. If is defined as some certain value , the corresponding frequency band can be extracted from the original signal. And also if we set , that is to say. we define the different factor and multiplied by the result of M-point FFT simultaneously to get multi-channel output , and so on. As shown in Figure 2, the dashed line means that we can add another more output channels if need.

#### 4. Implement in HF Radar System

In high frequency (3–30 MHz) ground (surface) wave radar, electromagnetic wave propagates along the ocean surface, in the lower frequency, the radar can reach a distance of 450 kilometers [9]. The propagation of surface wave is demonstrated in Figure 3.

As discussed above, appropriate sampling rate and repetition time are determined. In our HF radar system, ( = 8192) points are sampled in each sweep repetition period with sampling rate = 60 KHz (). During system test, a simulated “target” is generated by delaying and attenuating transmit signal, and feed it back into the receiver. The “target” (in frequency domain) appears at the 80th point, corresponding to a distance of

In the system, s, kHz/s, so we have a simulated target distance of 400 km, and the offset frequency is 300 Hz (), but the bandwidth of sampled data is ( kHz). After processing with new structure, we get 512 points of the first frequency segment (), and the analytic frequency band is decreased by times. , as shown in Figure 4(b).

**(a) Frequency points (1–8192)**

**(b) Frequency points (1–512)**

**(c) Frequency points (513–1024)**

If there is also a target at 1000th frequency point in the spectrum, the probable distance (propagating path) is nearly 3000 km. This might happen in Sky-wave Radar system, in which a certain range of distance is concerned. For example, Using once ionospheric reflection, an OTH (Over The Horizon) radar covers the range interval between about 1000 and 3500 km, as shown in Figure 5. So if is set to , factor . we can also get the second segment independently (Figure 4(c)). And the algorithm can be configured as multi-output structure, with different value, we can get corresponding output simultaneously.

The proposed algorithm is more efficient than the whole FFT calculation, the computing complexity of FFT is , while the complexity of proposed structure is for calculating . During the calculation in DSP or FPGA, FFT calculating block and parallel technique are used, so channels -point FFT can be processed simultaneously, less time is used for the processing in reality.

The conventional SRC method could also derive a certain frequency band from original signal, but the shape of digital filters (anti-imaging and anti-aliasing) is not as optimal as the proposed structure. When using conventional SRC method, with higher performance of roll-off characteristics, pass-band ripples and stop-band attenuation, higher stage number of filters is demanded [10]. However, it brings more complex computing. So the proposed method provides a better “filter” performance (actually, it is not a kind of filter, in some case, has a function of filter) and less computation.

#### 5. Realization of Modulation and Arbitrary Sampling Rate Conversion

The structure can be inversely used for modulation (interpolation), as shown in Figure 6, but the input data is -point frequency domain signal , with the structure (Figure 6), we can get -point time domain output signal , But the factor need to be changed from to , and is a value of , and then we take IFFT to these channels data to get the time domain sequences, interpolate them with zeros, and shift the interpolated data by respectively, at last add all the interpolated sequences, so we can get , the sampling frequency band increases by times.

And also we can input two or even more sequences, for example, we input two sequences , and multiplied with corresponding factors and , , after the multiplication with factors, we can add them and send into IFFT calculating block. So the two sequences are interpolated and modulated, so with the preset value, the input signal can be modulated by a certain pattern. Figure 7 demonstrates an interpolating example. Actually, the output result should be a time-domain sequence, but in order to explain the algorithm, we also give the spectrum of the output sequence. We set , and after the modulation, the input signals appear in the 2nd and 4th frequency band. The spectrum of output sequence is separated into frequency band as shown in (10).

**(a) Frequency points (1–512)**

**(b) Frequency points (1–512)**

**(c) Frequency points (1–8192)**

Combining with the decimation and interpolation methods, Arbitrary sampling rate conversion could be achieved, we define and (demo is abbr. of demodulation in Figure 2, mo is abbr of modulation in Figure 6). So the total conversion rate is , and also coding the frequency band unit (when certain pattern of , ,… and , are predefined) could be also achieved in some communication system if it is necessary, as shown in Figure 8. All these calculations are based on the fast-calculating of -point FFT (IFFT) block and parallel technique.

#### 6. Conclusion

This paper describes a demodulation method to extract the desired frequency band in FMCW Radar, which is an efficient method in some periodic transceivers like radar and sonar systems. It also provides a flexible method for the demodulation. Different frequency bands can be derived from input signal by setting corresponding value. And we can also modulate the signal to different frequency band by inversely using the structure. All these conversion can be achieved without filters used.

#### References

- A. G. Stove, “Linear FMCW radar techniques,”
*IEE Proceedings F*, vol. 139, no. 5, pp. 343–350, 1992. View at: Google Scholar - S. J. Orfanidis,
*Introduction to Signal Processing*, Prentice Hall, Upper Saddle River, NJ, USA, 1996. - W. A. Abu-Al-Saud and G. L. Stüber, “Efficient sample rate conversion for software radio systems,”
*IEEE Transactions on Signal Processing*, vol. 54, no. 3, pp. 932–939, 2006. View at: Publisher Site | Google Scholar - D. E. Barrick, “FM/CW radar signals and digital processing,” Tech. Rep. ERL 283-WPL 26, National Oceanic and Atmospheric Administration, Boulder, Colo, USA, 1973. View at: Google Scholar
- A. E. Carr, L. G. Cuthbert, and A. D. Olver, “Digital signal processing for target detection FMCW radar,”
*IEE Proceedings F*, vol. 128, no. 5, pp. 331–336, 1981. View at: Google Scholar - B. J. Lipa and D. E. Barrick, “FMCW signal processing report for mirage systems,” Tech. Rep., National Oceanic and Atmospheric Administration, Boulder, Colo, USA, 1980. View at: Google Scholar
- R. H. Khan and D. K. Mitchell, “Waveform analysis for high-frequency FMICW radar,”
*IEE Proceedings F*, vol. 138, no. 5, pp. 411–419, 1991. View at: Google Scholar - R. de Wild, L. R. Nieuwkerk, and J. S. van Sinttruyen, “Method for partial spectrum computation,”
*IEE Proceedings F*, vol. 134, no. 7, pp. 659–666, 1987. View at: Google Scholar - D. W. Green,
*Extraction of wind speed from high frequency ground wave radar oceanic backscatter*, Ph.D. dissertation, Memorial University of Newfoundland, Newfoundland, Canada, 2005. - K. Walt,
*Mixed-Signal and DSP Design Techniques*, Elsevier, Newnes, Australia, 2003.

#### Copyright

Copyright © 2010 Wei Shen and Biyang Wen. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.