Journal of Electrical and Computer Engineering

Volume 2016 (2016), Article ID 6349341, 7 pages

http://dx.doi.org/10.1155/2016/6349341

## An Optimization Synchronization Algorithm for TDDM Signal

School of Information Science and Engineering, Shenyang Ligong University, Shenyang 110159, China

Received 31 May 2016; Accepted 5 September 2016

Academic Editor: Jit S. Mandeep

Copyright © 2016 Fang Liu and Yongxin Feng. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

#### Abstract

The time division data modulation (TDDM) mechanism is recommended to improve the communications quality and enhance the antijamming capability of the spread spectrum communication system, which will be used in the next generation global navigation satellite (GNSS) systems. According to the principle and the characteristics of TDDM signal, an optimization synchronization algorithm is proposed. In the new algorithm, the synchronization accuracy and environmental adaptability have been improved with the special local sequence structure, the multicorrelation processing, and the proportion threshold mechanism. Thus, the inversion estimation formula was established. The simulation results demonstrate that the new algorithm can eliminate the illegibility threat in the synchronization process and can adapt to a lower SNR. In addition, this algorithm is better than the traditional algorithms in terms of synchronization accuracy and adaptability.

#### 1. Introduction

To improve the communications quality and the antijamming capability of the spread spectrum communication system, the time division data modulation (TDDM) [1] mechanism is recommended based on the traditional modulation methods. The new mechanism will be used in the next generation global navigation satellite systems [2, 3], for example, the GPS-III [4, 5] system. The difference of the TDDM and the traditional modulation mechanism is that nondata element is permitted in the new signal, and the spread spectrum processing depends on the pseudonoise (PN) code odd or even scheduling. The typical TDDM principle is that the even sequences sign is the same as the PN code sign, whereas the odd sequence sign is uncertain. The uncertain factor will cause some illegibility problems in the signal synchronization processing, such as inconspicuous correlation peak and higher data inverse error.

If the traditional algorithms are applied in TDDM signal synchronization, the correlation peak will decrease to half of the autocorrelation function when the data inversion position is in the middle of the received signal, and the correlation result is the same as the cross-correlation function when the data sign is successive negative. Thus, the approximate noncorrelation characteristic appears in this TDDM signal receiving. Currently, several PN code receiving [6, 7] and detection [8] technologies have been proposed, which can provide some referenced methods for TDDM signals synchronization. And the synchronization circuit system [9] based on field programmable gate array has become one of the development directions for GPS and even for a GNSS embedded real-time software receiver. Furthermore, large numbers of synchronization algorithms are proposed to improve the navigation signals receiving capability. For example, in [10], an efficient differential coherent accumulation algorithm for weak GPS signal bit synchronization was presented to reduce the computational load by approximately sixfold. In [11], the authors provided a detailed analysis of the significance of the cell-correlation phenomenon in MF correlates for the two widely used signal families in GNSS, namely, BPSK and BOC; next, the theoretical analysis was validated by Monte Carlo simulations. In [12], the code acquisition architecture for GNSS was presented to reduce the buffer resource required without reducing the numbers of code, frequency, and satellite bins. In [13], the authors proposed to reconstruct the correlation results of DBZP to improve the detection performance of the previously published double-block zero-padding (DBZP) method for weak GNSS long PN code signals.

In summary, from the perspective of algorithm generality, the TDDM signal synchronization algorithm is usually divided into two categories, namely, the filled zero (FZ) algorithm [14] and the positive-negative (PN) algorithm [15]. The principle of the FZ algorithm is that the odd bits of the local code are replaced by zero, and then the correlation arithmetic is executed by using the preprocessed receiving signal and the local signal. This algorithm reduces the uncertainty factor and enhances the estimation inversion precision by sacrificing the correlation peak in the synchronization processing. The principle of the PN algorithm is that the local code is processed by the positive and negative TDDM mechanism, and next, the correlation arithmetic is executed by using the preprocessed receiving signal and the positive local sequence. This algorithm imports the inversion judgment mechanism and combines the correlation peaks of the two channels to estimate the inversion position. The FZ algorithm and PN algorithm can be applied to receive TDDM signal and to estimate the inversion position, but the estimation precision of these algorithms is expected to improve in a complicated environment.

#### 2. The Optimization Synchronization Algorithm with Illegibility Elimination

To describe the new algorithm, the digital intermediate frequency received signal is modeled after frequency downconversion, ADC, and band-pass filtering. The processed signal is expressed aswhere is the binary data, is the TD codes, is the intermediate frequency due to the downconversion, is the Doppler frequency, and is the band-limited mixed noise signals. is the number of the received signal.

To eliminate the data inversion illegibility threat, we structure the special local sequences. The local sequence is produced using the same principle with the PN code of the received signal, and it is denoted as . The phase of the local code is expressed as variable , for which the initialization value is set as . Furthermore, the filling zero sequence is produced and expressed as , in which the odd number sequence is zero and the even number sequence is the same as ; these processes are expressed aswith

The preprocessing received signal is executed by the in-phase channel and quadrature channel frequency compensation arithmetic to overcome the influence of the uncertain frequency. The processing is expressed as

The two-channel compensated signals are processed using low-pass filtering, which are given by

The local code phase is moved from to , and next, the filling zero sequence is, respectively, multiplied by the received signal and . These quantities are given by

Combining the product results of the two channels, the square sum is calculated to inhibit the Doppler influence and then to achieve the correlation purpose. The processing is expressed as

From (7), we can see that the influences of Doppler and wave have been restrained. Furthermore, the correlation results are obtained using the change of variable , so the correlation sequence is expressed as

Although the existing algorithms can automatically adjust the threshold, they cannot improve the correlation peak values. Thus, we structure the proportion peak to improve the new algorithm adaptability. We define the proportion peak as

Thus, the peak judgment operation is performed after the proportion peak processing. If the proportion peak cannot exceed the threshold , then reacquisition will be operated after the local PN codes and adjusted Doppler shift, or else the value of is calculated using the proportion peak . Let the calculated be ; namely, . Thus, the calculated is imported to formula (2), and the results are expressed as

The received signal is multiplied by the new local signals and , whose results are given by (11) and (12). Thus, the accumulative totals are given by (13) and (14):

In this condition, let be the correlation result of the even number sequence when the data sign is negative, and let be the influence coefficient, which is given by (15). At the same time, let be the correlation result of the even number sequence when the data sign is positive, and let be the influence coefficient, which is given by (16):

In this paper, the theoretical correlation result between the local sequence and the received signal is defined as

In mixed noise condition, the relationship between the correlation result and , , , and can been given by

In view of these characteristics and combining (18) and (19), we can calculate the sequence number of the same sign as

Furthermore, the relationship between the real correlation and the theoretical correlation result is given by (21), and then the influence coefficient is calculated and given by (22):

We can rectify formula (20) as (23), and then we obtain the formula (24), according to the relationship of the theoretical correlation result and the processing number. Thus, formula (23) is renewed as (25):

In view of the same relation of the odd number and the even number, the sum of the positive sign and the negative sign is equal to the processing number . Finally, the inversion estimation formula is established to calculate the reversal position combining the above formulas, and the estimation reversal position is expressed as

#### 3. Simulation and Analysis

##### 3.1. The Capability Analysis

To furnish the judgment criterion for the synchronization algorithms, the thresholds for the new algorithm and the existing algorithms are ascertained. These algorithms are analyzed using the following parameters: 5 MHz PN code frequency, 10 MHz intermediate wave frequency, 40 MHz sampling frequency, and 50 bps data rate. In this simulation condition, three algorithms’ thresholds are as high as 10.

The ratio of the actual inversion position to the total length is defined as the data reversal rate. And with changing data reversal rate, the synchronization proportion peak change is shown in Figure 1. The results show that the new algorithm proportion peak can exceed 10 and can achieve the threshold required when the data sign is from positive to negative or is from negative to positive. With changing data reversal rate, the changes of the estimated reversal position and the theoretical reversal position are shown in Figure 2, the results indicate that the estimated value is approximately equal to the theoretical value. Furthermore, there may be some error between the estimated inversion position and the actual inversion position, so the estimated reversal error is tested. With changing actual data reversal rate, the estimated reversal error change is shown in Figure 3, in which -axis is the ratio of the actual inversion position to the total length and -axis is the estimated error between the estimated inversion position and the actual inversion position. The results show that the error is highest when the actual data reversal position is in the middle of the received signal; however, all errors can be less than the level.