Research Article  Open Access
Comparison between PhaseShift FullBridge Converters with Noncoupled and Coupled CurrentDoubler Rectifier
Abstract
This paper presents comparison between phaseshift fullbridge converters with noncoupled and coupled currentdoubler rectifier. In high current capability and high stepdown voltage conversion, a phaseshift fullbridge converter with a conventional currentdoubler rectifier has the common limitations of extremely low duty ratio and high component stresses. To overcome these limitations, a phaseshift fullbridge converter with a noncoupled currentdoubler rectifier (NCDR) or a coupled currentdoubler rectifier (CCDR) is, respectively, proposed and implemented. In this study, performance analysis and efficiency obtained from a 500 W phaseshift fullbridge converter with two improved currentdoubler rectifiers are presented and compared. From their prototypes, experimental results have verified that the phaseshift fullbridge converter with NCDR has optimal duty ratio, lower component stresses, and output current ripple. In component count and efficiency comparison, CCDR has fewer components and higher efficiency at full load condition. For small size and high efficiency requirements, CCDR is relatively suitable for high stepdown voltage and high efficiency applications.
1. Introduction
In a decentralized power system, the front end ac/dc converter is generally composed of two stages, in which one is a power factor correction (PFC) and the other is an intermediate dc/dc converter, as shown in Figure 1. Most of PFC circuits adopt a boost converter [1], and an intermediate converter is usually with an isolated version [2]. Using a boost converter can achieve a unity power factory, and using an isolated converter can provide galvanic isolation and high output current. In offline applications, universal ac voltage is always into dc 400 V as a dc bus by boost converters, and an intermediate dc/dc converter converts it to a low voltage bus of 24 V_{dc} or 12 V_{dc}. Therefore, for high output current and low output voltage applications, an isolated dc/dc converter is usually required.
To achieve low output voltage, high output current, and high efficiency, a phaseshift fullbridge converter with conventional currentdoubler rectifier is widely used in mediumhigh power condition, as shown in Figure 2 [3]. Nevertheless, it still has several limitations. For example, for high stepdown voltage conversion, it requires a transformer with high turns ratio or it has to reduce the duty ratio of the switches. A high turns ratio will result in high duty loss and low conversion efficiency, while a low duty ratio will increase input peak current and component stress [4]. The other limitation is that its large external resonant inductor will induce a large circulation current, which will flow through the primary winding of the transformer and the switches during a freewheeling interval. As a result, conduction loss in the switches and copper loss in the transformer are significant. To release the abovementioned limitations of the conventional fullbridge converter with currentdoubler, many approaches have been conducted [3–7]. However, their high stepdown voltage ratio still result in extremely low duty ratio, which will induce high peak current through the secondary winding of the isolation transformer and output filter inductors, increasing copper loss and component stresses [8–12].
To solve the abovementioned problem, the phaseshift fullbridge converter with NCDR or CCDR is proposed, as shown in Figures 3 and 4 [13]. They can alleviate the drawbacks of extremely low duty ratio and high component stresses. The two proposed improved rectifiers can extend duty ratio of the active switches to reduce the peak current through the secondary winding of the transformer and lower output current ripple. The conversion efficiency can be increased significantly. Section 2 describes derivation and operational principle of the two proposed improved currentdoubler rectifiers. Section 3 compares the benefits of the two improved currentdoubler rectifiers. Power loss and efficiency estimation are described in Section 4. Experimental results obtained from a 500 W phaseshift fullbridge converter with NCDR and CCDR are presented in Section 5. Finally, a conclusion is given in Section 6.
2. Derivation of Improved CurrentDoubler Rectifiers
With duality method, NCDR can be derived from a voltagequadrupler circuit, and coupleddoubler can be derived from a voltagedoubler circuits. In the following, derivations of both improved currentdoubler rectifiers are described in details.
2.1. Derivation of NCDR
Derivation of NCDR is based on a conventional voltagequadrupler circuit, as shown in Figure 5(a). According to duality principle, meshes of the voltage quadrupler are replaced with nodes, and capacitors are replaced with inductors, while diodes are with no change, yielding the proposed NCDR as shown in Figure 5(b).
2.2. Derivation of CCDR
Similarly, derivation of CCDR is based on a conventional voltagedoubler circuit, as shown in Figure 6(a). According to duality principle, meshes of the voltage doubler are replaced with nodes, and capacitors are replaced with inductors, while diodes are with no change, yielding the conventional currentdoubler rectifier as shown in Figure 6(b). Utilizing coupled inductor concept, the output filter inductors can be extended to the coupled ones, as shown in Figure 6(c).
3. Operational Principles of NCDR and CCDR
For NCDR and CCDR, each of which has its own merits and demerits. To have an objective judgment, operational principles of NCDR and CCDR are briefly described as follows.
3.1. Operational Principle of NCDR
In Figure 3, the proposed phaseshift fullbridge converter with NCDR under continuous inductor current operation can be divided into four major operating modes over a half switching cycle. Figure 7 shows conceptual voltage and current waveforms relative to key components of NCDR. and are denoted as the effective and loss duty ratios, respectively. is the voltage across the resonant inductor and the isolationtransformer primary winding, is the voltage across the isolationtransformer secondary winding, is the secondary current, and are the current of the energy inductors, and are the current of the output filter inductors, and are the current of the rectifier diodes. To simplify description of the steadystate operational modes, the phaseshift fullbridge converter will not be discussed in this section. Only the proposed NCDR is analyzed. Under continuous inductor current operation, four major operating modes of the NCDR are identified over a half switching cycle. Figure 8 shows equivalent circuits of the NCDR operational modes.
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Mode 1 (Figure 8(a), ). At time , a positive voltage crosses the secondary winding of transformer . First of all, diode is reversely biased and , , and are conducting. During this interval, inductor current flowing through the path is linearly increased, and inductor currents and are linearly decreased.
Mode 2 (Figure 8(b), ). At time , the secondary current is equal to inductor current , and diode is reversely biased. Inductor current flowing through the path is linearly increased, while the energy stored in inductor and will be released through the rectifier diode and to the load, respectively.
Mode 3 (Figure 8(c), ). When voltage drops to zero at time , all of the diodes () are conducting. During this interval, the inductor current flowing through two paths and and the inductor current flowing through are linearly decreased.
Mode 4 (Figure 8(d), ). At time , a negative voltage will cross the resonant inductor and the primary winding of transformer , since rectifier diode currents and have not been commutated completely yet. Therefore, all of the diodes () are maintained conducting, while inductor currents and are maintained discharging to the load.
At time , rectifier diode currents and have been commutated completely. Then, a positive voltage crosses the secondary winding of transformer . This ends a half switching cycle operation.
3.2. Operational Principle of CCDR
In Figure 4, each coupled inductor individually functions as a tapped inductor or a transformer during one switching cycle. In other words, the upper coupledinductor is charged during the charging period, which functions as a tapped inductor, while the lower coupledinductor functions as a transformer. Therefore, Figure 4 can be redrawn as shown in Figure 9. The proposed phaseshift fullbridge converter with CCDR under continuous inductor current operation can be divided into three major operating modes over a half switching cycle. Figure 10 shows conceptual voltage and current waveforms relative to key components of the converter. and are denoted as the effective and lost duty ratios, respectively. is the voltage across the resonant inductor and the isolationtransformer primary winding, is the voltage across the isolationtransformer secondary winding, is the secondary current, and are the current and voltage of the coupledinductor winding , and are the current and voltage of the rectifier diode, and is the output current. The circuit operation is explained as follows.
Mode 1 (Figure 11(a), ). At time , currents and are commutated completely. Then, a positive voltage crosses the secondary winding of transformer ; diode is reversely biased, and inductor current flowing through the path of increases linearly. During this interval, the energy stored in inductor will be released to the load through coupled inductor , and inductor current flowing through the path of is decreased. Meanwhile, inductors and function as a tapped inductor, while inductors and are coupled to function as a transformer .
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Mode 2 (Figure 11(b), ). When voltage drops to zero at time , the energy stored in inductor is no longer released to the load through coupled inductor . Therefore, inductor current will be gradually decreased, rectifier diodes and are conducted, and rectifier diode currents and begin commutating. During this freewheeling interval, inductor currents and decrease linearly.
Mode 3 (Figure 11(c), ). At time , a negative voltage will cross resonant inductor and the primary winding of transformer , since rectifier diode currents and have not been commutated completely yet. Therefore, the two rectifier diodes and are maintained conducting, while inductors and are discharged through diodes and , respectively.
When currents and are commutated completely at time , the converter operation over a half switching cycle is completed.
4. Performance Comparison between NCDR and CCDR
This section will compare both the features and characteristics of NCDR as well as CCDR, which include secondary winding peak current of transformer, voltage gain, and output current ripple.
4.1. Performance of NCDR
From Figures 3 and 7, during one complete switching cycle, the secondary winding peak current can be expressed as follows: where , is secondary voltage of transformer, and the voltage stresses of freewheeling diodes can be expressed as follows: where is output voltage. By applying the voltsecond balance principle to the auxiliary inductors and output filter inductors, the voltage gain of the proposed rectifier then can be derived as follows: where is duty ratio of power switches. From Figure 7 again, by using the interleaved current of the output inductors and , the output current ripple can be expressed: where is switching frequency of power switches.
4.2. Performance of CCDR
From Figures 9 and 10, during one complete switching cycle, the secondary winding peak current can be expressed as follows: where , and the voltage stresses of freewheeling diodes can be expressed as follows: where is turns ratio of coupled inductors. By applying the voltsecond balance principle to the auxiliary inductors and output filter inductors, the voltage gain of the proposed rectifier then can be derived as follows: From Figure 10 again, by combining the currents of and , output current ripple can be determined as
To objectively judge the merits and demerits of NCDR and CCDR, their performances are compared as summarized in Table 1 and Figure 12, assuming that the two improved currentdoubler rectifiers can be operated with identical frequency, the same input and output voltages, and load currents.

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5. Experimental Results
To verity the performance of NCDR and CCDR, two sets of 500 W prototypes with phaseshift fullbridge converters were built (see Figures 13 and 14). The specifications are listed as follows:(i)input voltage : 400 V_{dc},(ii)output current : 42 A,(iii)output voltage : 12 V_{dc}.(iv)output power : 500 W,(v)switching frequency : 100 kHz.
Figure 15 shows measured transformer waveforms of NCDR and CCDR under full load condition. From these measured waveforms, it can be seen that NCDR and CCDR can be extended duty ratio. Comparing between NCDR and CCDR, the NCDR has a wide duty ratio. Figure 16 shows waveforms of output filter inductors and for NCDR and CCDR, from which it can be seen that NCDR has lower inductor current ripple. Figure 17 shows waveforms of fullload output current, from which it can be seen that NCDR has lower output current ripple. Figure 18 shows the comparison of efficiency measurements between NCDR and CCDR, from which it can be seen that CCDR can achieve higher efficiency at heavy load and can reach as high as 91%. The reason behind is that NCDR is used with four inductors resulting in low conversion efficiency.
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6. Conclusions
In this paper, the proposed phaseshift fullbridge converter with NCDR and CCDR under 500 W has been implemented. The NCDR has the merits of extended duty ratio, lower output current ripple, and lower rectifier diodes voltage stresses, which can reduce the peak current through the isolation transformer and switches. However, in comparison between efficiency of NCDR and CCDR, the NCDR has lower efficiency at full load condition. The reason behind is that NCDR is used with four inductors resulting in low conversion efficiency. For small size and high efficiency requirements, CCDR is relatively suitable for high stepdown voltage and high power conversion applications.
Conflict of Interests
The authors declare that there is no conflict of interests regarding the publication of this paper.
Acknowledgment
This work was supported by the National Science Council, Taiwan, under Grant no. NSC1022221E167024.
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Copyright
Copyright © 2013 ChengTao Tsai et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.