Research Article | Open Access

# Output Information Based Fault-Tolerant Iterative Learning Control for Dual-Rate Sampling Process with Disturbances and Output Delay

**Academic Editor:**Andrzej Swierniak

#### Abstract

For a class of single-input single-output (SISO) dual-rate sampling processes with disturbances and output delay, this paper presents a robust fault-tolerant iterative learning control algorithm based on output information. Firstly, the dual-rate sampling process with output delay is transformed into discrete system in state-space model form with slow sampling rate without time delay by using lifting technology; then output information based fault-tolerant iterative learning control scheme is designed and the control process is turned into an equivalent two-dimensional (2D) repetitive process. Moreover, based on the repetitive process stability theory, the sufficient conditions for the stability of system and the design method of robust controller are given in terms of linear matrix inequalities (LMIs) technique. Finally, the flow control simulations of two flow tanks in series demonstrate the feasibility and effectiveness of the proposed method.

#### 1. Introduction

In industrial applications, many engineering plants operate in continuous time while the system inputs and outputs are sampled, yielding discrete-time signals. Moreover, due to the hardware limitations, process characteristics, and other reasons, sampling each variable with the same frequency is not necessary and realistic. Therefore, the measurable output and input information is usually sampled in different rates from different types of sensors, manual sampling, or laboratory analyses [1, 2]. These systems are often termed as multirate sampling process and dual-rate sampling process is a special case; sometimes the sampling periods of the slow rate sampled variables are integer multiples of the fast rate sampled ones [3]. For example, the control of the bottom and top composition products of a distillation column by acting on the reflux and vapor flow rates is a typical case, where the input control signals can be rapidly adjusted, while the infrequent and delayed composition measurements are only obtained by gas chromatography [4]. In some vehicle control systems, displacement and velocity are measured by using ultrasonic sensors; the two different groups of sensors are located at different locations of the vehicle and have different sampling periods [5]. During the last several decades, this corresponding control problem has attracted considerable attention, including the model identification [6â€“8] and control algorithms [9â€“11]. But the control problem of dual-rate sampling systems still has achieved relatively little research results compared with the single-rate sampling case. Moreover, to the best of our knowledge, there are few papers dealing with iterative learning control (ILC) problems for dual-rate sampling process with time delay and actuator fault.

The idea of ILC arose from Uchiyama in 1978 [12]; it represents a powerful approach for high performance tracking control of systems, which execute the same task over a finite duration repeatedly with a given desired trajectory and reset to the starting location once each execution is complete. Each execution of the task is known as a trial, or pass, and its duration is termed the trial length. ILC is currently mainly used to control single-rate sampling process. Compared with standard control scheme, the distinguishing feature of the ILC dynamic sequence of operations is to use the information from previous trials to update the control signal applied on the next one; the major advantage of ILC is the ability to improve system performance from trial to trial and include temporal information from previous trials that would be noncausal in standard systems. Over the past few decades, ILC has drawn significant research attention and increasingly been employed in many industrial processes, such as traffic system [13], networked stochastic system [14], robotic manipulator system [15], multiagent system [16], chemical pharmaceutical crystallization [17], and industrial injection molding batch processes [18].

The design of an ILC law starts, as always, with performance specifications where the novel feature for ILC is the reference trajectory or vector, which is assumed to be the same for all trials in most of the ILC literature. In the case of discrete dynamics, let , denote the output and input, respectively, on trial ; denotes the sampling number over the trial duration. Then if the error on trial is , where denotes the reference signal, and the basic ILC design problem is to construct a sequence of input function that forces the error sequence and input sequence to converge to zero and , respectively, or to within an acceptable tolerance, is termed learned control. It is a common approach to ILC design for discrete dynamics to use the lifting technique [19]. For the SISO systems with a nature extension to the multiple-input multiple-output (MIMO) systems, the input and output on any trial can be represented by supervectors formed by assembling the values at the sample instants into a column vector. Once the ILC law is applied, the propagation of the error can be represented by a linear difference equation and discrete linear systems theory can be utilized for trial-to-trial error convergence analysis and control law design.

Given the finite trial length, trial-to-trial error convergence can occur even if the system is unstable since such a system can only produce a bounded output over a finite time duration. Literature reviews [20â€“22] confirm that an alternative approach to ILC design is to first apply a feedback control law to produce acceptable dynamics along the trial and then apply ILC to accomplish trial-to-trial error convergence of the resulting 2D system. A drawback of the two-step synthesis procedure is that it does not lead to an optimal combination of the feedback and feedforward actions. Based on an abstract model in a Banach space setting, repetitive process is a particular subclass of 2D system that operates over a subset of the upper right quadrant of the 2D plane and is characterized by a series of sweeps, or passes, through a set of dynamics defined over a finite duration known as the pass length. It is a nature setting for ILC analysis and design; the main advantage is that it gives a systematic way to simultaneously consider behaviour along the time axis and from trial to trial [23]. A detailed treatment of the dynamics of these processes, including their origins in the modeling of mining operations, can be found in [24].

Time delay is also frequently encountered in the transmission of material or information between different parts of a system, including biology, chemistry, economics, population dynamics, and engineering applications. Time delay is one of the main causes of instability and poor performance in process control systems [25, 26], and currently many ILC algorithms have been applied to time delay single-rate sampling process by treating them as batch processes in a finite time on every trial. For example, a robust 2D closed-loop ILC combined with the output feedback scheme has been applied to batch processes with state delay and time-varying uncertainties [27, 28]. Composite iterative learning feedback controllers combined with state and output information are designed in [29]; then the sufficient conditions for delay dependent stability are obtained. However, these proposed methods are just based on the single-rate sampling process model, so that they cannot be directly applied to dual-rate sampling processes. Furthermore, these methods only use consistent slow sampling data and do not fully utilize all sampling data with different sampling intervals to improve control performance.

Moreover, the involved industrial control systems under challenging environment are vulnerable to faults. A fault in a single component may have major efforts on the large system as a whole. Actuator faults will reduce the stability and performance of control systems and may even cause complete breakdown of these systems. Fault-tolerant control is a special action that ensures a fail-safe operation under real-time conditions if components in the control system fail or become faulty [30]. Fault-tolerant ILC design which is sensitive to faults is especially required in application for ILC scheme due to the repeated nature of the control actuator. The extensions to deal with faults for ILC systems receive increasing attentions [31, 32]. For example, a robust fault-tolerant iterative learning control design method is proposed and illustrated by an electric motor system in [31] and also [32] gives iterative learning fault-tolerant control for a class of linear differential time delay uncertain systems with actuator faults in finite frequency domains. The challenge of fault-tolerant control here is how to design a reliable ILC scheme against fault based on the inconsistent dual-rate sampling input and output information with time delay.

This paper develops new results for ILC design applied to time delay dual-rate sampling process with the following contributions:(i)The output information based ILC law design is extended to the fault-tolerant control problem for dual-rate sampling process with time delay and actuator faults.(ii)Monotonic trial-to-trial error convergence conditions for the controlled ILC dynamics are derived.(iii)Robust control issue for disturbance attenuation performance is solved.

This paper is organized as follows: Section 2 describes a dual-rate sampling process with output delay and disturbance in the ILC setting by the state-space model with actuator faults; then it is transformed into a discrete system model form in slow sampling rate without time delay by using the lifting technology. Section 3 formulates the output information based fault-tolerant ILC design problem in the repetitive process setting. Some repetitive process stability theories are given as background in Section 4. Then the sufficient conditions for the stability of the controlled dynamic and the design method of robust controller are analyzed and given in corresponding linear matrix inequalities form in Section 5. Section 6 verifies the effectiveness of the proposed method by the flow control simulations of two flow tanks in series. Finally, some conclusions are given in Section 7.

Throughout this paper, the null and identity matrices with the required dimensions are denoted by 0 and , respectively, and the notation (resp., ) is used to represent the negative definite (resp., positive definite) matrix The notation denotes the transpose of elements in the symmetric position in a matrix. The symbol denotes a block-diagonal matrix with diagonal blocks and . The symbol represents the largest integer which is less than or equal to .

#### 2. System Description

Consider a class of SISO linear continuous processes in Figure 1 with output delay and disturbance; system dynamics are described in the ILC setting by the following state-space model:where the symbol denotes the trial number, is the fixed and finite trial length, , , , and are the system state, input, output, and disturbance vectors, respectively, is the time delay constant, and , , , and are system matrices of appropriate dimensions. Without loss of generality, assume , , on each trial.

To include actuator faults, let represent the failed actuator with the following fault model [32]:where the actuator failure parameter is unknown, but it satisfies the following condition:The parameters , () in this fault model, are assumed to be known. When , it corresponds to the normal case ; when , it covers the outage case; and correspond to partial failures, for example, partial degradation of an actuator or the abnormal case when the faulty actuator output is larger than the normal controller output. Introduceand define ; then by using (4), the unknown failure parameter can be written aswhereTherefore, the continuous process of (1) with actuator fault can be described by

For process (7), the discrete-time signal with sampling period is maintained as a continuous-time input signal using a zero-order hold in Figure 1; thenthe continuous-time output signal is sampled by a sampler with sampling period to get discrete-time output signal , where is the basic sampling period and and are the two positive coprime integers. For such a dual-rate sampling process, the measurable input-output data is ; , are unknown [33]. Moreover, in order to obtain the system model of dual-rate sampling process, the continuous process is first discretized with sampling period to obtain the discrete system model :where , , , and , .

For process , let be the frame period to denote the cycle sampling period of the system, then using symbol instead of in (9), we haveSimilarly, we can directly obtainaccording to (8), (11) can be simplified asSubstituting (10) into (12) and defining , where we assume , we have

*Remark 1. *The assumption condition can usually be satisfied for some dual-rate sampling processes; this means the time delay exists in the sampling frame period. Furthermore, if , then more information of the time delay system can be obtained in a full frame period when the controller is designed for the sampling process in Figure 1.

In terms of lifting technology, defining the state expanding vector with dimensions, and the input and disturbance expanding vectors with dimensions,we can directly convert the dual-rate sampling system model (9) with output delay into a lifting linear discrete system model without delay in a single slow sampling rate ,whereWe can obviously find that although (17) is a slow sampling rate system with , every real control input variable of expanding vector in (16) is also updated with a relatively fast sampling period . Particularly, if we force the input variables to be updated just in slow sampling period , that is, , , then (17) can be described asthus we can get the discrete state-space model of the dual-rate sampling process (1) with one sampling period ; it is just a special form of (17):where

#### 3. ILC Law Design

For the discrete sampling system described by (17), design an ILC law that constructs the current trial input that is equal to the control input on the previous trial plus a corrective term, that is, a control law of the formwhere is the correction term computed using previous trial data. Given the reference signal , the error on trial isTo formulate the ILC design problem in the repetitive process setting, for analysis purpose only, we define the vectorsWithout loss of generality, it is assumed that and, due to the initial conditions assumed for (17),

Since we can just obtain measurable input and output signal for dual-rate sampling process, suppose that the modification term in the output information based ILC law (22) takes the formwhere and are the control law matrices to be determined. Moreover, by (22)â€“(26) the controlled ILC dynamics can be written in the form of discrete repetitive process aswhereThe state-space model (27) represents a linear discrete repetitive process with pass output and state vectors , respectively, once the initial conditions are specified, that is, the pass state initial vector , , and the initial pass profile .

*Remark 2. *It is important to stress that, with the ILC law (22) applied, the resulting controlled dynamics (27) are modeled by a linear repetitive process state-space model; the previous trial (pass) error affects the current trial (pass) error . Repetitive process is a particular class of 2D systems where a series of sweeps are made through a set of dynamics defined over a finite duration. Once each sweep is completed, the dynamics are reset and the next sweep starts. On any sweep, the output on the previous sweep explicitly contributes to the current sweep output and hence the link to ILC dynamics [24].

Next the representation of discrete repetitive processes and the associated stability theory are given as background.

#### 4. Repetitive Process Theory

The state-space model of a linear discrete repetitive process over the finite pass length iswhere, on pass , is the state vector, is the output vector, is the control input vector, and is the disturbance input vector. Iffor any integers , then is in space, denoted by . To complete the process description, it is necessary to specify the boundary conditions, that is, the pass state initial vector sequence , and the initial pass profile

Define the shift operators , along the pass and pass-to-pass directions acting, for example, on and , respectively, asthen the 2D characteristic polynomial for processes described by (29) is defined asthe stability along the pass holds if and only ifwhereThis reversely promotes the development of LMI based stability condition along the pass which are sufficient but not necessary.

Lemma 3 (see [24]). *A linear discrete repetitive process described by (29) is stable along the pass if there exists a block-diagonal matrix such that the following LMI holds:whereis the so-called augmented plant matrix.*

*Definition 4. *A linear discrete repetitive process described by (29) is said to have robust disturbance attenuation if it is stable along the pass andNow consider the 2D transfer function matrix coupling the disturbance and current pass profile vectors which is given byand then the 2D Parseval theorem, which states that (37) is equivalent to the requirement thatwhere denotes the maximum singular value [34].

#### 5. Stability Analysis

The following lemmas are used in the proofs of the main results.

Lemma 5 (Schur complement formula [35]). *Given a symmetric matrix , and are square matrices, and then the following inequalities are equivalent:*(i)*.*(ii)* and .*(iii)* and .*

Lemma 6 (see [36]). *Given matrices , , , and of compatible dimensions, thenfor all satisfying if and only if there exists some such that*

Theorem 7. *Assume repetitive disturbance exists in dual-rate sampling process , that is, in discrete repetitive process (27); for any , output information based ILC scheme described as (27) under an actuator fault of the form (3)â€“(6) is stable along the trial, if there exist matrices , , , and such thathold, where , , andthen the corresponding matrices in output information based control law (26) are given by*

*Proof. *According to Lemma 3, we have , where , andApplying Lemma 5 (Schurâ€™s complement formula) to givesIntroduce and , and pre- and postmultiply (47) by matrix to yieldDue to and , we can rewrite (48) aswherethen by Lemma 6 and (6), inequality (49) is feasible if and only ifholds, where ; then application of Schurâ€™s complement formula to (51) givesPre- and postmultiplying the above inequality by and applying condition (42) immediately give the LMI of (43). This completes proof of the theorem.

Suppose nonrepetitive disturbance exists in dual-rate sampling process , that is, in repetitive process (27); then the robust disturbance attenuation performance (37) should be modified asconsequently, we can have the following result for robust controller design.

Theorem 8. *Assume ; for any , output information based ILC scheme described as a discrete linear repetitive process of the form (27) under an actuator fault of the form (3)â€“(6) is stable along the trial and has disturbance attenuation ; hence if there exist matrices , , , and such thatholds, where , , are given in (44), , , and the robust control law matrices and are given by (45).*

*Proof. *Suppose there exists robust disturbance attenuation if the associated Hamiltonian functionholds, where is the associated increment of Lyapunov function for repetitive process (27):where , , andIt is clear that (55) requires and hence the result of Lemma 3 holds. Using (27), it is easily shown thatwhereand and . Applying the Schur complement formula to (59) and defining giveMoreover, pre- and postmultiplying (60) by and its transpose, respectively, we havetherefore, (61) also can be modified aswhereSimilar to the proof of Theorem 7, another application of Lemmas 6 and 5 immediately gives (54).

The following analysis is to prove the robust disturbance attenuation . For any positive integers , , when all the initial conditions and in (57) are assumed to be zero, we haveUsing (55) and (64) yieldsthen (53) is satisfied; this means the ILC control process (27) has robust disturbance attenuation and the proof is complete.

It should be emphasized that condition (42) is not an inequality form; it cannot be directly solved by LMI tools. Therefore, one can first determine , , , and by solving the LMI (43) or (54) and then getwhere is the right inverse of matrix . However, in some cases, it is impossible to obtain the matrix by using the above formulation. Therefore, condition (42) in Theorems 7 and 8 can be converted into the following inequality [37]:where is a sufficiently small positive scalar. Observe that if the value of the scalar is sufficiently small, condition (42) is approximately satisfied. Thus one obtains the LMI condition using the Schur complement formula:

#### 6. Case Study

To illustrate the validity of the proposed design method, a system of two noninteracting flow tanks in series including pipelines and valves is considered for process control [38]. The material balance equations that govern the system in the disturbance-free and fault-free case shown in Figure 2 arewhere and are the cross-sectional areas of tanks 1 and 2, unmeasurable states and are the liquid levels for tanks 1 and 2, and are constants which depend on the valves, and input is the measured inlet flow rate. Meantime, amplifier element is used when the measured output signal outlet flow rate is very small and nominally equal to . Thus (69) can be written in state-space formwhere

Due to the differences of distance between the control points of tanks and flow rates to the sensors at the bottom of each tank, output time delay commonly appears in the system, which gives rise to instability and poor performance. Consider the case where the unknown external bounded disturbance stream (Stream 6 in Figure 2) is introduced into tank 2 for . The state-space form (71) becomeswhere represents the unknown external bounded disturbance stream and is the fixed delay. In the following simulations, the model parameters used are , , , , , the input updating time and the output sampling period , and then frame period . Applying the Euler concretization method with a sampling period to (72) results in the following discrete system model of the form (9), where

Partial degradation and wear from repeated control operation can lead to faults arising during the trials and it is assumed that an actuator fault occurs in the operation valve. As a numerical example, it is assumed that ; hence and . Suppose no actuator faults occur before trials have elapsed. Applying the lifting technology, this dual-rate sampling tank model can be converted into a lifting linear discrete model of the form (17), whereIf we also force the input variable to be just updated in slow sampling period , then and ; hence the dual-rate sampling tank model can be of the form (19), where , , , .

The initial state vector on each trial is assumed to be zero, , and the reference trajectory is

Introduce the root mean square (RMS) to evaluate tracking performance from trial to trial:where the smaller the value of , the better the tracking performance along the th trial. Next two possible scenarios are considered.

*Scenario 1 (repetitive disturbance with a constant fault). *It is assumed that in this scenario; hence . Consider the case when the operating valve is always partially blocked in tank system (9). This constant partial fault causes the actuator to drop to 80% of its normal value; hence . For single-rate sampling system model with matrices , using LMI toolbox to solve inequality (68) in Theorem 7 gives the corresponding matrices in (45) as