Eliminating the Effect of Common-Mode Voltage on an Open-End Winding PMSM Based on Model Predictive Torque Control

Lin, Zhiming; Lei, Bicheng; Wu, Lingwei; Mei, Pan

doi:https://doi.org/10.1155/2021/5516290

Mathematical Problems in Engineering

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Research Article | Open Access

Volume 2021 | Article ID 5516290 | https://doi.org/10.1155/2021/5516290

Eliminating the Effect of Common-Mode Voltage on an Open-End Winding PMSM Based on Model Predictive Torque Control

Zhiming Lin,¹Bicheng Lei,¹Lingwei Wu,^1,2and Pan Mei¹

Academic Editor: Xiaodong Sun

Received25 Jan 2021

Revised24 Mar 2021

Accepted18 Apr 2021

Published07 Jun 2021

Abstract

In the open-end winding permanent magnet synchronous motor (OEW-PMSM) with common DC link, the common-mode voltage (CMV) will cause leakage current and zero-sequence current, which will lead to the decrease in the system life and efficiency. To solve this problem, the loop characteristics of leakage current and zero-sequence current were analyzed, and the condition for eliminating the leakage current and the zero-sequence current was deduced. Then, the CMV of the voltage vectors for the OEW-PMSM system was calculated, and the appropriate voltage vectors satisfying the conditions were selected to form the control vector sets. Combined with the model predictive torque control (MPTC), a cost function without the weight factor was proposed. The voltage vector sets were predicted by the cost function. The optimal voltage vectors were selected to control the OEW-PMSM, which can eliminate the leakage current and the zero-sequence current caused by the CMV. The effectiveness of the proposed method was verified by the simulation results.

1. Introduction

Due to the advantages of high power, more voltage vectors, and high fault tolerance, open-end winding (OEW) motors have attracted wide attention in high-power, large-capacity, and vehicle applications [1–4]. In the OEW system, the inverter connected to both ends of the open winding often uses a single common DC power supply instead of two isolated power supplies for lower costs [2–4].

Since the inverter uses the pulse-width modulation (PWM) technology to drive the motor in the OEW, there exists common-mode voltage (CMV) in the motor winding. Through parasitic capacitive impedance, high-frequency CMV generates leakage current which will damage the shaft and bearing [5, 6]. Furthermore, CMV will cause zero-sequence current and reduce the efficiency of the OEW system because of being a zero-sequence loop in the common DC power supply of the OEW system [1, 2, 7, 8]. Therefore, zero-sequence current (ZSC) and leakage current caused by CMV should be eliminated in the system.

As CMV frequency reduces, the leakage current of the system will also be reduced. A method proposed in [9, 10] uses three vectors with the same CMV to synthesize the reference voltage to reduce the CMV frequency. An active zero-state PWM method can reduce the CMV frequency by replacing the zero vector with two vectors in the opposite direction [11]. Based on the principle of volt-second, Kalaiselvi and Srinivas [12] proposed a hybrid PWM switching method to reduce CMV and leakage current for the OEW system. All these methods have a vector modulation process, which is complex.

In addition to the vector synthesis technique, there are also other methods to solve this problem. A multilevel method has been presented to eliminate CMV and leakage current in [13–15]. Chokes are used as filters to eliminate leakage current caused by CMV in [16–18]. Some protective aluminium films are added between the stator and the rotor to prevent leakage current caused by CMV in [19]. All these methods need extra hardware.

As for ZSC reducing in OEW, a modulation for the considered topology which is able to eliminate the ZSC is proposed in [7]. The duration time of the active voltage vectors is redistributed to the suppression of ZSC in [8]. A space-vector PWM scheme with the capability of zero-sequence voltage control is proposed to eliminate the ZSC in [4].

These aforementioned methods can only eliminate ZSC or leakage current, but cannot eliminate both at the same time. Due to different mechanisms of leakage current and ZSC generated by CMV, few literature studies can simultaneously eliminate the influence of CMV on leakage current and ZSC.

A method to simultaneously eliminate the influence of CMV on ZSC and leakage current in the OEW-PMSM is proposed in this paper. Different from the aforementioned method that requires vector modulation or additional hardware, this method only needs to select a suitable vector set according to certain conditions and then use the selected vector set in MPTC to control the OEW system. Meanwhile, when applying MPTC, a cost function without weight factors is proposed. The method is simple and easy to implement, and the effectiveness and feasibility of the proposed method are verified by simulation.

2. Model of the OEW-PMSM Drive System

The structure of the OEW-PMSM system with common DC link is shown in Figure 1. The system is fed by two-level inverters VSI1 and VSI2. Because of the existing zero-sequence loop, different voltages of CMV between the two inverters will produce zero-sequence current i₀. At the same time, the CMV with high frequency can produce leakage current i_L because of the existing parasitic capacitive impedance between the phase windings, motor frame, and bearing [5].

The stator voltage equations of the OEW-PMSM can be expressed aswhere u_d, u_q, u₀, i_d, i_q, i₀, L_d, L_q, and L₀ are the stator voltage, current, and inductance components in the d-, q-, and 0-axis, respectively, R_s is the stator resistance, ω_r is the electrical angular speed, and Ψ_f is the rotor flux linkage.

The flux and torque equations of the OEW-PMSM are expressed as

It is easy to obtain the phase voltages u_a, u_b, and u_c across the phase winding from Figure 1 aswhere (S_a1, S_a2, S_b1, S_a2, S_c1, S_c2)∈(0, 1) are the switching state of six legs. S_a1 = 0 indicates that the upper leg switch is off and the lower leg switch is on, and u_a1 = 0. If S_a1 = 1, the leg switch state is opposite, and u_a1 = U_dc. The other legs are similar.

The CMV of the two inverters is defined as [7]

Then, the voltage of the zero-sequence loop can be further expressed as [12]

The voltage of the leakage current loop is defined as [12]

For parasitic capacitive impedance in the leakage current loop, as it is known, current i_L can be expressed as

Equations (2) and (6)–(8) show that, in order to eliminate the influence of CMV on the system, for the zero-sequence loop, when CMV1 = CMV2, u₀ = 0, and CMV will not generate zero-sequence current i₀. And for parasitic capacitive impedance C_L of the leakage current loop, as long as u_L = C (C is constant), it means that the frequency of u_L is zero, and CMV will not generate current i_L on C_L.

Therefore, the condition of eliminating the influence of CMV on both zero-sequence loop and leakage current loop is obtained aswhere C is a constant.

3. Voltage Vector Selection

In Figure 1, each inverter has eight voltage vectors, including six nonzero voltage vectors and two zero voltage vectors. The voltage vectors of the two inverters can be expressed by (10) and (11), and the amplitude of six nonzero voltage vectors is 2U_dc/3.

The distribution of space voltage vectors is shown in Figure 2 for each inverter.

(a)

(b)

From the structure of the two inverters in Figure 1, it can be seen that the synthesized voltage vectors of the two inverters can be expressed as

The synthesized voltage vectors of the two inverters are 64 vectors, including 56 nonzero voltage vectors and 8 zero voltage vectors. The synthesized voltage vectors can be seen in Figure 3, where the amplitude of six large voltage vectors is 4U_dc/3, the amplitude of twelve medium voltage vectors is , and the amplitude of thirty-six small voltage vectors is 2U_dc/3.

For each voltage vector in Figure 3, CMV1 and CMV2 can be calculated according to (5), and then u_L and u₀ can be calculated according to (6) and (7). For example, CMV1 and CMV2 of voltage vector 4-1′ are calculated as follows:

Then, u_L and u₀ are calculated as follows:

In order to obtain the voltage vector sets that meet condition (9), u_L and u₀ of each voltage vector in Figure 3 are calculated firstly. Secondly, the voltage vectors with u₀ = 0 are chosen, and then they are classified according to the value of u_L. Finally, two voltage vector sets meeting condition (9) can be obtained as shown in Table 1. These two voltage vector sets include nonzero medium voltage vectors (row 1, 3) and zero voltage vectors (row 2, 4). These six nonzero medium voltage vectors in each set can form a voltage vector circle. Therefore, these two voltage vector sets can be used to control the OEW-PMSM.

From Table 1, it can been seen that set-I consists of nonzero medium voltage vectors in row 1 and zero voltage vectors in row 2, in which u₀ is always zero and u_L is always 2U_dc/3. Set-II consists of nonzero medium voltage vectors in row 3 and zero voltage vectors in row 4, in which u₀ is always zero and u_L is always U_dc/3.

4. Model Predictive Torque Control

Because of the fast dynamic response and flexible cost function configuration, the model predictive control (MPC) has developed rapidly in recent years [20, 21]. Meanwhile, MPC has also been used to eliminate ZSC in [22, 23].

In order to achieve better performance, voltage vector sets I and II are applied to MPTC to control the OEW-PMSM system. According to the forward Euler method, the prediction model of the OEW-PMSM can be obtained. The current prediction equations can be expressed as

Meanwhile, flux and torque prediction equations are as follows:

The traditional cost function of MPTC is as follows [22]:

When (17) is used as the cost function, it is difficult to tune weighting factor λ in practical applications. Generally, the value of λ is related to and . If and change dynamically in the process of application, λ should also be changed correspondingly in order to achieve the best performance. In order to solve this problem, a new and simplified cost function is proposed as

There is no weighting factor in (18). Especially, in practical applications, when and change, (18) can adapt automatically without changing. If is equal to 0, it can be replaced by a small number, such as 1e − 3.

The block diagram of the MPTC for the OEW-PMSM is shown in Figure 4.

The proposed MPTC selects an optimal vector from set-I or set-II according to the minimum value of the cost function (18) in each control cycle. If the optimal vector is a zero voltage vector, it should be selected according to the principle of minimum switching times from set-I or set-II.

5. Simulation Studies

The proposed method is verified by simulation with a sampling frequency of 100 kHz. In the simulation, six large voltage vectors and one zero vector from Figure 3 are selected as set-III for comparison as shown in Table 2.

In the simulation, the surface-mounted PMSM is taken as an example. The parameters of the PMSM are listed in Table 3. The speed is set to 1000 r/min, and the common DC voltage is 150 V. The initial torque is set to 5 N m. Then, after 0.05 seconds, the torque is increased to 15 N m. The sampling frequency is set to 100 kHz, and predictive control is performed every sampling period.

The simulation results are shown in Figures 5–7.

(a)

(b)

(c)

(a)

(b)

(c)

(a)

(b)

(c)

It can be seen from Figure 5 that the dynamic response of speed and torque is fast for all sets. The phase current is smooth for set-I and set-II. However, the phase current of set-III is distorted, and it means there is some harmonic current included in this phase current.

u₀ of the three sets shown in Figure 6 is consistent with the analysis in Tables 1 and 2. Because u₀ of set-I and set-II is 0, i₀ generated by set-I and set-II is also 0. u₀ of set-III varies between −U_dc/3(50 V) and U_dc/3(50 V), and R_s (1.2 Ω) is small. Therefore, i₀ generated by set-III is large, and the phase current generated by set-III is distorted in Figure 5(c).

The results of u_L shown in Figure 7 are also consistent with Tables 1 and 2. For set-I and set-II, u_L is 2U_dc/3 (100 V) and U_dc/3(50 V), respectively, and the amplitude of u_L is constant, which cannot generate current i_L. Therefore, i_L is 0 in set-I and set-II. However, there exists i_L in set-III because u_L of set-III varies between U_dc/2(75 V) and 0.

In addition, in the simulation, the switching frequencies of the three schemes are counted. Sets I, II, and III are 77.56 kHz, 77.77 kHz, and 53.44 kHz, respectively. Set-I and set-II are slightly smaller than the sampling period, and set-III is close to half of the sampling period.

From the figures, it can be seen that set-I and set-II can eliminate the influence of CMV on leakage current and zero-sequence current in the OEW-PMSM. Compared with set-III, in set-I and set-II, the zero-sequence current i₀ can be reduced from the amplitude of 30 A to 0, and the leakage current i_L can be reduced from 10 mA to 0. Moreover, set-II has smaller u_L than that of set-I, but set-III has a smaller switching frequency.

6. Conclusions

For the OEW-PMSM system with common DC link, a MPTC method is proposed to eliminate the zero-sequence current and the leakage current caused by CMV. In this method, the voltage vector in the OEW-PMSM with the same CMV is selected to form the control vector sets. When the MPTC uses the vector sets to control the OEW-PMSM, the CMV of the zero-sequence current loop can be reduced to zero and the CMV of the leakage current loop can be kept constant. Therefore, the zero-sequence current and the leakage current caused by CMV can be eliminated without vector modulation. Meanwhile, the proposed cost function without the weight factor makes the distribution that there is no need to debug the weighting factor when deploying MPTC. Simulation results verify the feasibility and effectiveness of the method.

For the three-phase OEW motor system, the zero-sequence loop consists of two inverters and stator winding, and the leakage current loop consists of stator winding and parasitic capacitive impedance. This paper takes the PMSM as the research object, but the proposed method can also be applied to the induction motor (IM) and PMSM with the same structure on the two loops.

Data Availability

All the data, together with relevant analysis scripts and files, are available from the corresponding author (e-mail: [email protected]) upon request.

Conflicts of Interest

The authors declare no conflicts of interest regarding the publication of this study.

Acknowledgments

The authors thank Dr. Dan Sun at Zhejiang University for her valuable comments on their manuscript. This work was supported in part by the Youth Fund of Zhejiang Provincial Natural Science Foundation (Grant no. LQ21F030002) and the Jiangsu Provincial Postdoctoral Science Foundation (Grant no. 2020Z230).

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Copyright © 2021 Zhiming Lin et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

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